Apparatus for transmitting broadcast signals, apparatus for receiving broadcast signals, method for transmitting broadcast signals and method for receiving broadcast signals

ABSTRACT

A method and an apparatus for transmitting broadcast signals thereof are disclosed. The apparatus for transmitting broadcast signals comprises an encoder encoding service data, a time interleaver interleaving the encoded service data, a mapper mapping the interleaved service data into a plurality of OFDM (Orthogonal Frequency Division Multiplex) symbols to build at least one signal frame, a frequency interleaver interleaving data in the at least one signal frame by using a different interleaving-seed which is used for every OFDM symbol pair comprised of two sequential OFDM symbols, wherein the frequency interleaver calculates an interleaving address for the different interleaving-seed based on a main-PRBS sequence and a cyclic shifting value, a modulator modulating the frequency interleaved data by an OFDM scheme and a transmitter transmitting the broadcast signals having the modulated data, wherein an interleaving-seed is generated based on a cyclic shift value and an FFT size of the modulating.

This application is a Continuation of application Ser. No. 14/924,199filed on Oct. 27, 2015, which is a Continuation of application Ser. No.14/551,728, filed on Nov. 24, 2014, now U.S. Pat. No. 9,210,022, issuedon Dec. 8, 2015, and claims priority to U.S. Provisional ApplicationNos. 61/923,766, 61/923,767, 61/923,768, 61/923,769, 61/923,771 filed onJan. 6, 2014 and U.S. Provisional Application No. 61/908,719 filed onNov. 25, 2013 all of which are incorporated by reference in theirentirety therein.

BACKGROUND OF THE INVENTION

Field of the Invention

The present invention relates to an apparatus for transmitting broadcastsignals, an apparatus for receiving broadcast signals and methods fortransmitting and receiving broadcast signals.

Discussion of the Related Art

As analog broadcast signal transmission comes to an end, varioustechnologies for transmitting/receiving digital broadcast signals arebeing developed. A digital broadcast signal may include a larger amountof video/audio data than an analog broadcast signal and further includevarious types of additional data in addition to the video/audio data.

That is, a digital broadcast system can provide HD (high definition)images, multi-channel audio and various additional services. However,data transmission efficiency for transmission of large amounts of data,robustness of transmission/reception networks and network flexibility inconsideration of mobile reception equipment need to be improved fordigital broadcast.

SUMMARY OF THE INVENTION

Accordingly, the present invention is directed to an apparatus fortransmitting broadcast signals and an apparatus for receiving broadcastsignals for future broadcast services and methods for transmitting andreceiving broadcast signals for future broadcast services.

An object of the present invention is to provide an apparatus and methodfor transmitting broadcast signals to multiplex data of a broadcasttransmission/reception system providing two or more different broadcastservices in a time domain and transmit the multiplexed data through thesame RF signal bandwidth and an apparatus and method for receivingbroadcast signals corresponding thereto.

Another object of the present invention is to provide an apparatus fortransmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals toclassify data corresponding to services by components, transmit datacorresponding to each component as a data pipe, receive and process thedata

Still another object of the present invention is to provide an apparatusfor transmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals tosignal signaling information necessary to provide broadcast signals.

Technical Solution

To achieve the object and other advantages and in accordance with thepurpose of the invention, as embodied and broadly described herein, amethod for transmitting broadcast signals includes encoding servicedata, time interleaving the encoded service data, mapping the timeinterleaved service data into a plurality of OFDM (Orthogonal FrequencyDivision Multiplex) symbols to build at least one signal frame,frequency interleaving data in the at least one signal frame by using adifferent interleaving-seed which is used for every OFDM symbol paircomprised of two sequential OFDM symbols, wherein the frequencyinterleaving further includes calculating an interleaving address forthe different interleaving-seed based on a main-PRBS sequence and acyclic shifting value, modulating the frequency interleaved data by theOFDM scheme and transmitting the broadcast signals having the modulateddata.

Advantageous Effects

The present invention can process data according to servicecharacteristics to control QoS for each service or service component,thereby providing various broadcast services.

The present invention can achieve transmission flexibility bytransmitting various broadcast services through the same RF signalbandwidth.

The present invention can improve data transmission efficiency andincrease robustness of transmission/reception of broadcast signals usinga MIMO system.

According to the present invention, it is possible to provide broadcastsignal transmission and reception methods and apparatus capable ofreceiving digital broadcast signals without error even with mobilereception equipment or in an indoor environment.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are included to provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this application, illustrate embodiment(s) of the invention andtogether with the description serve to explain the principle of theinvention. In the drawings:

FIG. 1 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

FIGS. 2 a and b illustrate an input formatting block according to oneembodiment of the present invention.

FIG. 3 illustrates an input formatting block according to anotherembodiment of the present invention.

FIG. 4 illustrates an input formatting block according to anotherembodiment of the present invention.

FIGS. 5a and b illustrate a BICM block according to an embodiment of thepresent invention.

FIG. 6 illustrates a BICM block according to another embodiment of thepresent invention.

FIG. 7 illustrates a frame building block according to one embodiment ofthe present invention.

FIG. 8 illustrates an OFMD generation block according to an embodimentof the present invention.

FIG. 9 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

FIGS. 10 a, b, c and d illustrate frame structures according to anembodiment of the present invention.

FIG. 11 illustrates a signaling hierarchy structure of the frameaccording to an embodiment of the present invention.

FIG. 12 illustrates preamble signaling data according to an embodimentof the present invention.

FIG. 13 illustrates PLS1 data according to an embodiment of the presentinvention.

FIG. 14 illustrates PLS2 data according to an embodiment of the presentinvention.

FIG. 15 illustrates PLS2 data according to another embodiment of thepresent invention.

FIG. 16 illustrates a logical structure of a frame according to anembodiment of the present invention.

FIG. 17 illustrates PLS mapping according to an embodiment of thepresent invention.

FIG. 18 illustrates EAC mapping according to an embodiment of thepresent invention.

FIGS. 19 a and b illustrate FIC mapping according to an embodiment ofthe present invention.

FIGS. 20 a and b illustrate types of DP according to an embodiment ofthe present invention.

FIGS. 21 a and b illustrate DP mapping according to an embodiment of thepresent invention.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention.

FIG. 23 illustrates a bit interleaving according to an embodiment of thepresent invention.

FIGS. 24 a and b illustrate cell-word demultiplexing according to anembodiment of the present invention.

FIGS. 25a, b and c illustrate time interleaving according to anembodiment of the present invention.

FIGS. 26 a and b illustrate the basic operation of a twisted row-columnblock interleaver according to an embodiment of the present invention.

FIG. 27 illustrates an operation of a twisted row-column blockinterleaver according to another embodiment of the present invention.

FIG. 28 illustrates a diagonal-wise reading pattern of a twistedrow-column block interleaver according to an embodiment of the presentinvention.

FIG. 29 illustrates interleaved XFECBLOCKs from each interleaving arrayaccording to an embodiment of the present invention.

FIG. 30 is a view illustrating an operation of a frequency interleaver7020 according to an embodiment of the present invention.

FIG. 31 illustrates a basic switch model for MUX and DEMUX proceduresaccording to an embodiment of the present invention.

FIG. 32 illustrates an operation of a memory bank according to anembodiment of the present invention.

FIG. 33 illustrates a frequency deinterleaving procedure according to anembodiment of the present invention.

FIG. 34 is a view illustrates concept of frequency interleaving appliedto a single signal frame according to an embodiment of the presentinvention.

FIG. 35 is a view illustrating logical operation mechanism of frequencyinterleaving applied to a single signal frame according to an embodimentof the present invention.

FIG. 36 illustrates expressions of logical operation mechanism offrequency interleaving applied to a single signal frame according to anembodiment of the present invention.

FIG. 37 is a view illustrating single-memory deinterleaving for inputsequential OFDM symbols.

FIG. 38 is a view illustrating an interleaving process according toaccording to an embodiment of the present invention.

FIG. 39 illustrates expressions of the interleaved OFDM symbol pairaccording to an embodiment of the present invention.

FIG. 40 illustrates expressions representing an operation of themain-PRBS generator according to an embodiment of the present invention.

FIG. 41 illustrates expressions representing an operation of thesub-PRBS generator according to an embodiment of the present invention.

FIG. 42 illustrates expressions representing an operation of calculatingthe interleaving address and the cyclic shifting value according to anembodiment of the present invention.

FIGS. 43 a and b illustrate table representing parameters related to thefrequency interleaving according to an embodiment of the presentinvention.

FIG. 44 illustrates expressions illustrating an interleaving-addressgenerator for 8K FFT mode according to an embodiment of the presentinvention.

FIG. 45 illustrates expressions illustrating an interleaving-addressgenerator for 16K FFT mode according to an embodiment of the presentinvention.

FIG. 46 illustrates expressions illustrating an interleaving-addressgenerator for 32K FFT mode according to an embodiment of the presentinvention.

FIG. 47 is a view of a 1K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

FIGS. 48 a and b illustrate expressions representing an operation of a1K FFT mode main-sequence generator and symbol-offset generatoraccording to an embodiment of the present invention.

FIG. 49 is a view illustrating a 1K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

FIGS. 50 a and b are expressions representing operations of 1K FFT modebit shuffling and 1K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

FIG. 51 is a view of a 2K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

FIGS. 52 a and b illustrate expressions representing an operation of a2K FFT mode main-sequence generator and symbol-offset generatoraccording to an embodiment of the present invention.

FIG. 53 is a view illustrating a 2K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

FIGS. 54 a and b are expressions representing operations of 2K FFT modebit shuffling and 2K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

FIG. 55 is a view of a 4K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

FIGS. 56 a and b illustrate expressions representing an operation of a4K FFT mode main-sequence generator and symbol-offset generatoraccording to an embodiment of the present invention.

FIG. 57 is a view illustrating a 4K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

FIGS. 58 a and b are expressions representing operations of 4K FFT modebit shuffling and 4K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

FIG. 59 is a view of an 8K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

FIGS. 60 a and b illustrate expressions representing an operations of an8K FFT mode main-sequence generator and symbol-offset generatoraccording to an embodiment of the present invention.

FIG. 61 is a view illustrating an 8K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

FIGS. 62 a and b are expressions representing operations of 8K FFT modebit shuffling and 8K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

FIG. 63 is a view of a 16K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

FIGS. 64 a and b illustrate expressions representing an operation of a16K FFT mode main-sequence generator and symbol-offset generatoraccording to an embodiment of the present invention.

FIG. 65 is a view illustrating a 16K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

FIGS. 66 a and b are expressions representing operations of 16K FFT modebit shuffling and 16K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

FIG. 67 is a view of a 32K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

FIGS. 68 a and b illustrate expressions representing an operations of a32K FFT mode main-sequence generator and symbol-offset generatoraccording to an embodiment of the present invention.

FIG. 69 is a view illustrating a 32K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

FIGS. 70 a and b are expressions representing operations of 32K FFT modebit shuffling and 32K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

FIG. 71 is a flowchart illustrating a method for transmitting broadcastsignals according to an embodiment of the present invention.

FIG. 72 is a flowchart illustrating a method for receiving broadcastsignals according to an embodiment of the present invention.

BEST MODE

Reference will now be made in detail to the preferred embodiments of thepresent invention, examples of which are illustrated in the accompanyingdrawings. The detailed description, which will be given below withreference to the accompanying drawings, is intended to explain exemplaryembodiments of the present invention, rather than to show the onlyembodiments that can be implemented according to the present invention.The following detailed description includes specific details in order toprovide a thorough understanding of the present invention. However, itwill be apparent to those skilled in the art that the present inventionmay be practiced without such specific details.

Although most terms used in the present invention have been selectedfrom general ones widely used in the art, some terms have beenarbitrarily selected by the applicant and their meanings are explainedin detail in the following description as needed. Thus, the presentinvention should be understood based upon the intended meanings of theterms rather than their simple names or meanings.

The present invention provides apparatuses and methods for transmittingand receiving broadcast signals for future broadcast services. Futurebroadcast services according to an embodiment of the present inventioninclude a terrestrial broadcast service, a mobile broadcast service, aUHDTV service, etc. The present invention may process broadcast signalsfor the future broadcast services through non-MIMO (Multiple InputMultiple Output) or MIMO according to one embodiment. A non-MIMO schemeaccording to an embodiment of the present invention may include a MISO(Multiple Input Single Output) scheme, a SISO (Single Input SingleOutput) scheme, etc.

While MISO or MIMO uses two antennas in the following for convenience ofdescription, the present invention is applicable to systems using two ormore antennas.

The present invention may defines three physical layer (PL)profiles—base, handheld and advanced profiles—each optimized to minimizereceiver complexity while attaining the performance required for aparticular use case. The physical layer (PHY) profiles are subsets ofall configurations that a corresponding receiver should implement.

The three PHY profiles share most of the functional blocks but differslightly in specific blocks and/or parameters. Additional PHY profilescan be defined in the future. For the system evolution, future profilescan also be multiplexed with the existing profiles in a single RFchannel through a future extension frame (FEF). The details of each PHYprofile are described below.

1. Base Profile

The base profile represents a main use case for fixed receiving devicesthat are usually connected to a roof-top antenna. The base profile alsoincludes portable devices that could be transported to a place butbelong to a relatively stationary reception category. Use of the baseprofile could be extended to handheld devices or even vehicular by someimproved implementations, but those use cases are not expected for thebase profile receiver operation.

Target SNR range of reception is from approximately 10 to 20 dB, whichincludes the 15 dB SNR reception capability of the existing broadcastsystem (e.g. ATSC A/53). The receiver complexity and power consumptionis not as critical as in the battery-operated handheld devices, whichwill use the handheld profile. Key system parameters for the baseprofile are listed in below table 1.

TABLE 1 LDPC codeword length 16K, 64K bits Constellation size 4~10 bpcu(bits per channel use) Time de-interleaving memory size ≦2¹⁹ data cellsPilot patterns Pilot pattern for fixed reception FFT size 16K, 32Kpoints

2. Handheld Profile

The handheld profile is designed for use in handheld and vehiculardevices that operate with battery power. The devices can be moving withpedestrian or vehicle speed. The power consumption as well as thereceiver complexity is very important for the implementation of thedevices of the handheld profile. The target SNR range of the handheldprofile is approximately 0 to 10 dB, but can be configured to reachbelow 0 dB when intended for deeper indoor reception.

In addition to low SNR capability, resilience to the Doppler Effectcaused by receiver mobility is the most important performance attributeof the handheld profile. Key system parameters for the handheld profileare listed in the below table 2.

TABLE 2 LDPC codeword length 16K bits Constellation size 2~8 bpcu Timede-interleaving memory size ≦2¹⁸ data cells Pilot patterns Pilotpatterns for mobile and indoor reception FFT size 8K, 16K points

3. Advanced Profile

The advanced profile provides highest channel capacity at the cost ofmore implementation complexity. This profile requires using MIMOtransmission and reception, and UHDTV service is a target use case forwhich this profile is specifically designed. The increased capacity canalso be used to allow an increased number of services in a givenbandwidth, e.g., multiple SDTV or HDTV services.

The target SNR range of the advanced profile is approximately 20 to 30dB. MIMO transmission may initially use existing elliptically-polarizedtransmission equipment, with extension to full-power cross-polarizedtransmission in the future. Key system parameters for the advancedprofile are listed in below table 3.

TABLE 3 LDPC codeword length 16K, 64K bits Constellation size 8~12 bpcuTime de-interleaving memory size ≦2¹⁹ data cells Pilot patterns Pilotpattern for fixed reception FFT size 16K, 32K points

The following terms and definitions may apply to the present invention.The following terms and definitions can be changed according to design.

auxiliary stream: sequence of cells carrying data of as yet undefinedmodulation and coding, which may be used for future extensions or asrequired by broadcasters or network operators

base data pipe: data pipe that carries service signaling data

baseband frame (or BBFRAME): set of K_(bch) bits which form the input toone FEC encoding process (BCH and LDPC encoding)

cell: modulation value that is carried by one carrier of the OFDMtransmission

coded block: LDPC-encoded block of PLS1 data or one of the LDPC-encodedblocks of PLS2 data

data pipe: logical channel in the physical layer that carries servicedata or related metadata, which may carry one or multiple service(s) orservice component(s).

data pipe unit: a basic unit for allocating data cells to a DP in aframe.

data symbol: OFDM symbol in a frame which is not a preamble symbol (theframe signaling symbol and frame edge symbol is included in the datasymbol)

DP_ID: this 8-bit field identifies uniquely a DP within the systemidentified by the SYSTEM_ID

dummy cell: cell carrying a pseudo-random value used to fill theremaining capacity not used for PLS signaling, DPs or auxiliary streams

emergency alert channel: part of a frame that carries EAS informationdata

frame: physical layer time slot that starts with a preamble and endswith a frame edge symbol

frame repetition unit: a set of frames belonging to same or differentphysical layer profile including a FEF, which is repeated eight times ina super-frame

fast information channel: a logical channel in a frame that carries themapping information between a service and the corresponding base DP

FECBLOCK: set of LDPC-encoded bits of a DP data

FFT size: nominal FFT size used for a particular mode, equal to theactive symbol period T_(S) expressed in cycles of the elementary periodT

frame signaling symbol: OFDM symbol with higher pilot density used atthe start of a frame in certain combinations of FFT size, guard intervaland scattered pilot pattern, which carries a part of the PLS data

frame edge symbol: OFDM symbol with higher pilot density used at the endof a frame in certain combinations of FFT size, guard interval andscattered pilot pattern

frame-group: the set of all the frames having the same PHY profile typein a super-frame.

future extension frame: physical layer time slot within the super-framethat could be used for future extension, which starts with a preamble

Futurecast UTB system: proposed physical layer broadcasting system, ofwhich the input is one or more MPEG2-TS or IP or general stream(s) andof which the output is an RF signal

input stream: A stream of data for an ensemble of services delivered tothe end users by the system.

normal data symbol: data symbol excluding the frame signaling symbol andthe frame edge symbol

PHY profile: subset of all configurations that a corresponding receivershould implement

PLS: physical layer signaling data consisting of PLS1 and PLS2

PLS1: a first set of PLS data carried in the FSS symbols having a fixedsize, coding and modulation, which carries basic information about thesystem as well as the parameters needed to decode the PLS2

NOTE: PLS1 data remains constant for the duration of a frame-group.

PLS2: a second set of PLS data transmitted in the FSS symbol, whichcarries more detailed PLS data about the system and the DPs

PLS2 dynamic data: PLS2 data that may dynamically change frame-by-frame

PLS2 static data: PLS2 data that remains static for the duration of aframe-group

preamble signaling data: signaling data carried by the preamble symboland used to identify the basic mode of the system

preamble symbol: fixed-length pilot symbol that carries basic PLS dataand is located in the beginning of a frame

NOTE: The preamble symbol is mainly used for fast initial band scan todetect the system signal, its timing, frequency offset, and FFT-size.

reserved for future use: not defined by the present document but may bedefined in future

super-frame: set of eight frame repetition units

time interleaving block (TI block): set of cells within which timeinterleaving is carried out, corresponding to one use of the timeinterleaver memory

TI group: unit over which dynamic capacity allocation for a particularDP is carried out, made up of an integer, dynamically varying number ofXFECBLOCKs

NOTE: The TI group may be mapped directly to one frame or may be mappedto multiple frames. It may contain one or more TI blocks.

Type 1 DP: DP of a frame where all DPs are mapped into the frame in TDMfashion

Type 2 DP: DP of a frame where all DPs are mapped into the frame in FDMfashion

XFECBLOCK: set of N cells carrying all the bits of one LDPC FECBLOCKcells

FIG. 1 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

The apparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can includean input formatting block 1000, a BICM (Bit interleaved coding &modulation) block 1010, a frame structure block 1020, an OFDM(Orthogonal Frequency Division Multiplexing) generation block 1030 and asignaling generation block 1040. A description will be given of theoperation of each module of the apparatus for transmitting broadcastsignals.

IP stream/packets and MPEG2-TS are the main input formats, other streamtypes are handled as General Streams. In addition to these data inputs,Management Information is input to control the scheduling and allocationof the corresponding bandwidth for each input stream. One or multiple TSstream(s), IP stream(s) and/or General Stream(s) inputs aresimultaneously allowed.

The input formatting block 1000 can demultiplex each input stream intoone or multiple data pipe(s), to each of which an independent coding andmodulation is applied. The data pipe (DP) is the basic unit forrobustness control, thereby affecting quality-of-service (QoS). One ormultiple service(s) or service component(s) can be carried by a singleDP. Details of operations of the input formatting block 1000 will bedescribed later.

The data pipe is a logical channel in the physical layer that carriesservice data or related metadata, which may carry one or multipleservice(s) or service component(s).

Also, the data pipe unit: a basic unit for allocating data cells to a DPin a frame.

In the BICM block 1010, parity data is added for error correction andthe encoded bit streams are mapped to complex-value constellationsymbols. The symbols are interleaved across a specific interleavingdepth that is used for the corresponding DP. For the advanced profile,MIMO encoding is performed in the BICM block 1010 and the additionaldata path is added at the output for MIMO transmission. Details ofoperations of the BICM block 1010 will be described later.

The Frame Building block 1020 can map the data cells of the input DPsinto the OFDM symbols within a frame. After mapping, the frequencyinterleaving is used for frequency-domain diversity, especially tocombat frequency-selective fading channels. Details of operations of theFrame Building block 1020 will be described later.

After inserting a preamble at the beginning of each frame, the OFDMGeneration block 1030 can apply conventional OFDM modulation having acyclic prefix as guard interval. For antenna space diversity, adistributed MISO scheme is applied across the transmitters. In addition,a Peak-to-Average Power Reduction (PAPR) scheme is performed in the timedomain. For flexible network planning, this proposal provides a set ofvarious FFT sizes, guard interval lengths and corresponding pilotpatterns. Details of operations of the OFDM Generation block 1030 willbe described later.

The Signaling Generation block 1040 can create physical layer signalinginformation used for the operation of each functional block. Thissignaling information is also transmitted so that the services ofinterest are properly recovered at the receiver side. Details ofoperations of the Signaling Generation block 1040 will be describedlater.

FIGS. 2, 3 and 4 illustrate the input formatting block 1000 according toembodiments of the present invention. A description will be given ofeach figure.

FIG. 2 illustrates an input formatting block according to one embodimentof the present invention. FIG. 2 shows an input formatting module whenthe input signal is a single input stream.

The input formatting block illustrated in FIG. 2 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

The input to the physical layer may be composed of one or multiple datastreams. Each data stream is carried by one DP. The mode adaptationmodules slice the incoming data stream into data fields of the basebandframe (BBF). The system supports three types of input data streams:MPEG2-TS, Internet protocol (IP) and Generic stream (GS). MPEG2-TS ischaracterized by fixed length (188 byte) packets with the first bytebeing a sync-byte (0x47). An IP stream is composed of variable length IPdatagram packets, as signaled within IP packet headers. The systemsupports both IPv4 and IPv6 for the IP stream. GS may be composed ofvariable length packets or constant length packets, signaled withinencapsulation packet headers.

(a) shows a mode adaptation block 2000 and a stream adaptation 2010 forsignal DP and (b) shows a PLS generation block 2020 and a PLS scrambler2030 for generating and processing PLS data. A description will be givenof the operation of each block.

The Input Stream Splitter splits the input TS, IP, GS streams intomultiple service or service component (audio, video, etc.) streams. Themode adaptation module 2010 is comprised of a CRC Encoder, BB (baseband)Frame Slicer, and BB Frame Header Insertion block.

The CRC Encoder provides three kinds of CRC encoding for error detectionat the user packet (UP) level, i.e., CRC-8, CRC-16, and CRC-32. Thecomputed CRC bytes are appended after the UP. CRC-8 is used for TSstream and CRC-32 for IP stream. If the GS stream doesn't provide theCRC encoding, the proposed CRC encoding should be applied.

BB Frame Slicer maps the input into an internal logical-bit format. Thefirst received bit is defined to be the MSB. The BB Frame Slicerallocates a number of input bits equal to the available data fieldcapacity. To allocate a number of input bits equal to the BBF payload,the UP packet stream is sliced to fit the data field of BBF.

BB Frame Header Insertion block can insert fixed length BBF header of 2bytes is inserted in front of the BB Frame. The BBF header is composedof STUFFI (1 bit), SYNCD (13 bits), and RFU (2 bits). In addition to thefixed 2-Byte BBF header, BBF can have an extension field (1 or 3 bytes)at the end of the 2-byte BBF header.

The stream adaptation 2010 is comprised of stuffing insertion block andBB scrambler.

The stuffing insertion block can insert stuffing field into a payload ofa BB frame. If the input data to the stream adaptation is sufficient tofill a BB-Frame, STUFFI is set to ‘0’ and the BBF has no stuffing field.Otherwise STUFFI is set to ‘1’ and the stuffing field is insertedimmediately after the BBF header. The stuffing field comprises two bytesof the stuffing field header and a variable size of stuffing data.

The BB scrambler scrambles complete BBF for energy dispersal. Thescrambling sequence is synchronous with the BBF. The scrambling sequenceis generated by the feed-back shift register.

The PLS generation block 2020 can generate physical layer signaling(PLS) data. The PLS provides the receiver with a means to accessphysical layer DPs. The PLS data consists of PLS1 data and PLS2 data.

The PLS1 data is a first set of PLS data carried in the FSS symbols inthe frame having a fixed size, coding and modulation, which carriesbasic information about the system as well as the parameters needed todecode the PLS2 data. The PLS1 data provides basic transmissionparameters including parameters required to enable the reception anddecoding of the PLS2 data. Also, the PLS1 data remains constant for theduration of a frame-group.

The PLS2 data is a second set of PLS data transmitted in the FSS symbol,which carries more detailed PLS data about the system and the DPs. ThePLS2 contains parameters that provide sufficient information for thereceiver to decode the desired DP. The PLS2 signaling further consistsof two types of parameters, PLS2 Static data (PLS2-STAT data) and PLS2dynamic data (PLS2-DYN data). The PLS2 Static data is PLS2 data thatremains static for the duration of a frame-group and the PLS2 dynamicdata is PLS2 data that may dynamically change frame-by-frame.

Details of the PLS data will be described later.

The PLS scrambler 2030 can scramble the generated PLS data for energydispersal.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 3 illustrates an input formatting block according to anotherembodiment of the present invention.

The input formatting block illustrated in FIG. 3 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

FIG. 3 shows a mode adaptation block of the input formatting block whenthe input signal corresponds to multiple input streams.

The mode adaptation block of the input formatting block for processingthe multiple input streams can independently process the multiple inputstreams.

Referring to FIG. 3, the mode adaptation block for respectivelyprocessing the multiple input streams can include an input streamsplitter 3000, an input stream synchronizer 3010, a compensating delayblock 3020, a null packet deletion block 3030, a head compression block3040, a CRC encoder 3050, a BB frame slicer 3060 and a BB headerinsertion block 3070. Description will be given of each block of themode adaptation block.

Operations of the CRC encoder 3050, BB frame slicer 3060 and BB headerinsertion block 3070 correspond to those of the CRC encoder, BB frameslicer and BB header insertion block described with reference to FIG. 2and thus description thereof is omitted.

The input stream splitter 3000 can split the input TS, IP, GS streamsinto multiple service or service component (audio, video, etc.) streams.

The input stream synchronizer 3010 may be referred as ISSY. The ISSY canprovide suitable means to guarantee Constant Bit Rate (CBR) and constantend-to-end transmission delay for any input data format. The ISSY isalways used for the case of multiple DPs carrying TS, and optionallyused for multiple DPs carrying GS streams.

The compensating delay block 3020 can delay the split TS packet streamfollowing the insertion of ISSY information to allow a TS packetrecombining mechanism without requiring additional memory in thereceiver.

The null packet deletion block 3030, is used only for the TS inputstream case. Some TS input streams or split TS streams may have a largenumber of null-packets present in order to accommodate VBR (variablebit-rate) services in a CBR TS stream. In this case, in order to avoidunnecessary transmission overhead, null-packets can be identified andnot transmitted. In the receiver, removed null-packets can bere-inserted in the exact place where they were originally by referenceto a deleted null-packet (DNP) counter that is inserted in thetransmission, thus guaranteeing constant bit-rate and avoiding the needfor time-stamp (PCR) updating.

The head compression block 3040 can provide packet header compression toincrease transmission efficiency for TS or IP input streams. Because thereceiver can have a priori information on certain parts of the header,this known information can be deleted in the transmitter.

For Transport Stream, the receiver has a-priori information about thesync-byte configuration (0x47) and the packet length (188 Byte). If theinput TS stream carries content that has only one PID, i.e., for onlyone service component (video, audio, etc.) or service sub-component (SVCbase layer, SVC enhancement layer, MVC base view or MVC dependentviews), TS packet header compression can be applied (optionally) to theTransport Stream. IP packet header compression is used optionally if theinput steam is an IP stream.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 4 illustrates an input formatting block according to anotherembodiment of the present invention.

The input formatting block illustrated in FIG. 4 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

FIG. 4 illustrates a stream adaptation block of the input formattingmodule when the input signal corresponds to multiple input streams.

Referring to FIG. 4, the mode adaptation block for respectivelyprocessing the multiple input streams can include a scheduler 4000, an1-Frame delay block 4010, a stuffing insertion block 4020, an in-bandsignaling 4030, a BB Frame scrambler 4040, a PLS generation block 4050and a PLS scrambler 4060. Description will be given of each block of thestream adaptation block.

Operations of the stuffing insertion block 4020, the BB Frame scrambler4040, the PLS generation block 4050 and the PLS scrambler 4060correspond to those of the stuffing insertion block, BB scrambler, PLSgeneration block and the PLS scrambler described with reference to FIG.2 and thus description thereof is omitted.

The scheduler 4000 can determine the overall cell allocation across theentire frame from the amount of FECBLOCKs of each DP. Including theallocation for PLS, EAC and FIC, the scheduler generate the values ofPLS2-DYN data, which is transmitted as in-band signaling or PLS cell inFSS of the frame. Details of FECBLOCK, EAC and FIC will be describedlater.

The 1-Frame delay block 4010 can delay the input data by onetransmission frame such that scheduling information about the next framecan be transmitted through the current frame for in-band signalinginformation to be inserted into the DPs.

The in-band signaling 4030 can insert un-delayed part of the PLS2 datainto a DP of a frame.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 5 illustrates a BICM block according to an embodiment of thepresent invention.

The BICM block illustrated in FIG. 5 corresponds to an embodiment of theBICM block 1010 described with reference to FIG. 1.

As described above, the apparatus for transmitting broadcast signals forfuture broadcast services according to an embodiment of the presentinvention can provide a terrestrial broadcast service, mobile broadcastservice, UHDTV service, etc.

Since QoS (quality of service) depends on characteristics of a serviceprovided by the apparatus for transmitting broadcast signals for futurebroadcast services according to an embodiment of the present invention,data corresponding to respective services needs to be processed throughdifferent schemes. Accordingly, the a BICM block according to anembodiment of the present invention can independently process DPs inputthereto by independently applying SISO, MISO and MIMO schemes to thedata pipes respectively corresponding to data paths. Consequently, theapparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can controlQoS for each service or service component transmitted through each DP.

(a) shows the BICM block shared by the base profile and the handheldprofile and

(b) shows the BICM block of the advanced profile.

The BICM block shared by the base profile and the handheld profile andthe BICM block of the advanced profile can include plural processingblocks for processing each DP.

A description will be given of each processing block of the BICM blockfor the base profile and the handheld profile and the BICM block for theadvanced profile.

A processing block 5000 of the BICM block for the base profile and thehandheld profile can include a Data FEC encoder 5010, a bit interleaver5020, a constellation mapper 5030, an SSD (Signal Space Diversity)encoding block 5040 and a time interleaver 5050.

The Data FEC encoder 5010 can perform the FEC encoding on the input BBFto generate FECBLOCK procedure using outer coding (BCH), and innercoding (LDPC). The outer coding (BCH) is optional coding method. Detailsof operations of the Data FEC encoder 5010 will be described later.

The bit interleaver 5020 can interleave outputs of the Data FEC encoder5010 to achieve optimized performance with combination of the LDPC codesand modulation scheme while providing an efficiently implementablestructure. Details of operations of the bit interleaver 5020 will bedescribed later.

The constellation mapper 5030 can modulate each cell word from the bitinterleaver 5020 in the base and the handheld profiles, or cell wordfrom the Cell-word demultiplexer 5010-1 in the advanced profile usingeither QPSK, QAM-16, non-uniform QAM (NUQ-64, NUQ-256, NUQ-1024) ornon-uniform constellation (NUC-16, NUC-64, NUC-256, NUC-1024) to give apower-normalized constellation point, e_(l). This constellation mappingis applied only for DPs. Observe that QAM-16 and NUQs are square shaped,while NUCs have arbitrary shape. When each constellation is rotated byany multiple of 90 degrees, the rotated constellation exactly overlapswith its original one. This “rotation-sense” symmetric property makesthe capacities and the average powers of the real and imaginarycomponents equal to each other. Both NUQs and NUCs are definedspecifically for each code rate and the particular one used is signaledby the parameter DP_MOD filed in PLS2 data.

The SSD encoding block 5040 can precode cells in two (2D), three (3D),and four (4D) dimensions to increase the reception robustness underdifficult fading conditions.

The time interleaver 5050 can operates at the DP level. The parametersof time interleaving (TI) may be set differently for each DP. Details ofoperations of the time interleaver 5050 will be described later.

A processing block 5000-1 of the BICM block for the advanced profile caninclude the Data FEC encoder, bit interleaver, constellation mapper, andtime interleaver. However, the processing block 5000-1 is distinguishedfrom the processing block 5000 further includes a cell-worddemultiplexer 5010-1 and a MIMO encoding block 5020-1.

Also, the operations of the Data FEC encoder, bit interleaver,constellation mapper, and time interleaver in the processing block5000-1 correspond to those of the Data FEC encoder 5010, bit interleaver5020, constellation mapper 5030, and time interleaver 5050 described andthus description thereof is omitted.

The cell-word demultiplexer 5010-1 is used for the DP of the advancedprofile to divide the single cell-word stream into dual cell-wordstreams for MIMO processing. Details of operations of the cell-worddemultiplexer 5010-1 will be described later.

The MIMO encoding block 5020-1 can processing the output of thecell-word demultiplexer 5010-1 using MIMO encoding scheme. The MIMOencoding scheme was optimized for broadcasting signal transmission. TheMIMO technology is a promising way to get a capacity increase but itdepends on channel characteristics. Especially for broadcasting, thestrong LOS component of the channel or a difference in the receivedsignal power between two antennas caused by different signal propagationcharacteristics makes it difficult to get capacity gain from MIMO. Theproposed MIMO encoding scheme overcomes this problem using arotation-based pre-coding and phase randomization of one of the MIMOoutput signals.

MIMO encoding is intended for a 2×2 MIMO system requiring at least twoantennas at both the transmitter and the receiver. Two MIMO encodingmodes are defined in this proposal; full-rate spatial multiplexing(FR-SM) and full-rate full-diversity spatial multiplexing (FRFD-SM). TheFR-SM encoding provides capacity increase with relatively smallcomplexity increase at the receiver side while the FRFD-SM encodingprovides capacity increase and additional diversity gain with a greatcomplexity increase at the receiver side. The proposed MIMO encodingscheme has no restriction on the antenna polarity configuration.

MIMO processing is required for the advanced profile frame, which meansall DPs in the advanced profile frame are processed by the MIMO encoder.MIMO processing is applied at DP level. Pairs of the ConstellationMapper outputs NUQ (e_(1,i) and e_(2,i)) are fed to the input of theMIMO Encoder. Paired MIMO Encoder output (g1,i and g2,i) is transmittedby the same carrier k and OFDM symbol l of their respective TX antennas.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 6 illustrates a BICM block according to another embodiment of thepresent invention.

The BICM block illustrated in FIG. 6 corresponds to an embodiment of theBICM block 1010 described with reference to FIG. 1.

FIG. 6 illustrates a BICM block for protection of physical layersignaling (PLS), emergency alert channel (EAC) and fast informationchannel (FIC). EAC is a part of a frame that carries EAS informationdata and FIC is a logical channel in a frame that carries the mappinginformation between a service and the corresponding base DP. Details ofthe EAC and FIC will be described later.

Referring to FIG. 6, the BICM block for protection of PLS, EAC and FICcan include a PLS FEC encoder 6000, a bit interleaver 6010, aconstellation mapper 6020 and a time interleaver 6030.

Also, the PLS FEC encoder 6000 can include a scrambler, BCHencoding/zero insertion block, LDPC encoding block and LDPC paritypuncturing block. Description will be given of each block of the BICMblock.

The PLS FEC encoder 6000 can encode the scrambled PLS 1/2 data, EAC andFIC section.

The scrambler can scramble PLS1 data and PLS2 data before BCH encodingand shortened and punctured LDPC encoding.

The BCH encoding/zero insertion block can perform outer encoding on thescrambled PLS 1/2 data using the shortened BCH code for PLS protectionand insert zero bits after the BCH encoding. For PLS1 data only, theoutput bits of the zero insertion may be permutted before LDPC encoding.

The LDPC encoding block can encode the output of the BCH encoding/zeroinsertion block using LDPC code. To generate a complete coded block,C_(ldpc), parity bits, P_(ldpc) are encoded systematically from eachzero-inserted PLS information block, I_(ldpc) and appended after it.C _(ldpc) =[I _(ldpc) P _(ldpc) ]=[i ₀ ,i ₁ , . . . ,i _(K) _(ldpc) ₋₁,p ₀ ,p ₁ , . . . ,p _(N) _(ldpc) _(-K) _(ldpc) ₋₁]  [Expression 1]

The LDPC code parameters for PLS1 and PLS2 are as following table 4.

TABLE 4 Signaling K_(ldpc) Type K_(sig) K_(bch) N_(bch)_parity(=N_(bch)) N_(ldpc) N_(ldpc)_parity code rate Q_(ldpc) PLS1 342 1020 601080 4320 3240 1/4 36 PLS2 <1021 >1020 2100 2160 7200 5040  3/10 56

The LDPC parity puncturing block can perform puncturing on the PLS1 dataand PLS 2 data.

When shortening is applied to the PLS1 data protection, some LDPC paritybits are punctured after LDPC encoding. Also, for the PLS2 dataprotection, the LDPC parity bits of PLS2 are punctured after LDPCencoding. These punctured bits are not transmitted.

The bit interleaver 6010 can interleave the each shortened and puncturedPLS1 data and PLS2 data.

The constellation mapper 6020 can map the bit interleaved PLS1 data andPLS2 data onto constellations.

The time interleaver 6030 can interleave the mapped PLS1 data and PLS2data. The time interleaver 6030 can be omitted.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 7 illustrates a frame building block according to one embodiment ofthe present invention.

The frame building block illustrated in FIG. 7 corresponds to anembodiment of the frame building block 1020 described with reference toFIG. 1.

Referring to FIG. 7, the frame building block can include a delaycompensation block 7000, a cell mapper 7010 and a frequency interleaver7020. Description will be given of each block of the frame buildingblock.

The delay compensation block 7000 can adjust the timing between the datapipes and the corresponding PLS data to ensure that they are co-timed atthe transmitter end. The PLS data is delayed by the same amount as datapipes are by addressing the delays of data pipes caused by the InputFormatting block and BICM block. The delay of the BICM block is mainlydue to the time interleaver 5050. In-band signaling data carriesinformation of the next TI group so that they are carried one frameahead of the DPs to be signaled. The Delay Compensating block delaysin-band signaling data accordingly.

The cell mapper 7010 can map PLS, EAC, FIC, DPs, auxiliary streams anddummy cells into the active carriers of the OFDM symbols in the frame.The basic function of the cell mapper 7010 is to map data cells producedby the TIs for each of the DPs, PLS cells, and EAC/FIC cells, if any,into arrays of active OFDM cells corresponding to each of the OFDMsymbols within a frame. Service signaling data (such as PSI (programspecific information)/SI) can be separately gathered and sent by a datapipe. The Cell Mapper operates according to the dynamic informationproduced by the scheduler and the configuration of the frame structure.Details of the frame will be described later.

The frequency interleaver 7020 can randomly interleave data cellsreceived from the cell mapper 7010 to provide frequency diversity. Also,the frequency interleaver 7020 can operate on very OFDM symbol paircomprised of two sequential OFDM symbols using a differentinterleaving-seed order to get maximum interleaving gain in a singleframe. Details of operations of the frequency interleaver 7020 will bedescribed later.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 8 illustrates an OFMD generation block according to an embodimentof the present invention.

The OFMD generation block illustrated in FIG. 8 corresponds to anembodiment of the OFMD generation block 1030 described with reference toFIG. 1.

The OFDM generation block modulates the OFDM carriers by the cellsproduced by the Frame Building block, inserts the pilots, and producesthe time domain signal for transmission. Also, this block subsequentlyinserts guard intervals, and applies PAPR (Peak-to-Average Power Radio)reduction processing to produce the final RF signal.

Referring to FIG. 8, the frame building block can include a pilot andreserved tone insertion block 8000, a 2D-eSFN encoding block 8010, anIFFT (Inverse Fast Fourier Transform) block 8020, a PAPR reduction block8030, a guard interval insertion block 8040, a preamble insertion block8050, other system insertion block 8060 and a DAC block 8070.Description will be given of each block of the frame building block.

The pilot and reserved tone insertion block 8000 can insert pilots andthe reserved tone.

Various cells within the OFDM symbol are modulated with referenceinformation, known as pilots, which have transmitted values known apriori in the receiver. The information of pilot cells is made up ofscattered pilots, continual pilots, edge pilots, FSS (frame signalingsymbol) pilots and FES (frame edge symbol) pilots. Each pilot istransmitted at a particular boosted power level according to pilot typeand pilot pattern. The value of the pilot information is derived from areference sequence, which is a series of values, one for eachtransmitted carrier on any given symbol. The pilots can be used forframe synchronization, frequency synchronization, time synchronization,channel estimation, and transmission mode identification, and also canbe used to follow the phase noise.

Reference information, taken from the reference sequence, is transmittedin scattered pilot cells in every symbol except the preamble, FSS andFES of the frame. Continual pilots are inserted in every symbol of theframe. The number and location of continual pilots depends on both theFFT size and the scattered pilot pattern. The edge carriers are edgepilots in every symbol except for the preamble symbol. They are insertedin order to allow frequency interpolation up to the edge of thespectrum. FSS pilots are inserted in FSS(s) and FES pilots are insertedin FES. They are inserted in order to allow time interpolation up to theedge of the frame.

The system according to an embodiment of the present invention supportsthe SFN network, where distributed MISO scheme is optionally used tosupport very robust transmission mode. The 2D-eSFN is a distributed MISOscheme that uses multiple TX antennas, each of which is located in thedifferent transmitter site in the SFN network.

The 2D-eSFN encoding block 8010 can process a 2D-eSFN processing todistorts the phase of the signals transmitted from multipletransmitters, in order to create both time and frequency diversity inthe SFN configuration. Hence, burst errors due to low flat fading ordeep-fading for a long time can be mitigated.

The IFFT block 8020 can modulate the output from the 2D-eSFN encodingblock 8010 using OFDM modulation scheme. Any cell in the data symbolswhich has not been designated as a pilot (or as a reserved tone) carriesone of the data cells from the frequency interleaver. The cells aremapped to OFDM carriers.

The PAPR reduction block 8030 can perform a PAPR reduction on inputsignal using various PAPR reduction algorithm in the time domain.

The guard interval insertion block 8040 can insert guard intervals andthe preamble insertion block 8050 can insert preamble in front of thesignal. Details of a structure of the preamble will be described later.The other system insertion block 8060 can multiplex signals of aplurality of broadcast transmission/reception systems in the time domainsuch that data of two or more different broadcast transmission/receptionsystems providing broadcast services can be simultaneously transmittedin the same RF signal bandwidth. In this case, the two or more differentbroadcast transmission/reception systems refer to systems providingdifferent broadcast services. The different broadcast services may referto a terrestrial broadcast service, mobile broadcast service, etc. Datarelated to respective broadcast services can be transmitted throughdifferent frames.

The DAC block 8070 can convert an input digital signal into an analogsignal and output the analog signal. The signal output from the DACblock 7800 can be transmitted through multiple output antennas accordingto the physical layer profiles. A Tx antenna according to an embodimentof the present invention can have vertical or horizontal polarity.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 9 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention cancorrespond to the apparatus for transmitting broadcast signals forfuture broadcast services, described with reference to FIG. 1.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention can includea synchronization & demodulation module 9000, a frame parsing module9010, a demapping & decoding module 9020, an output processor 9030 and asignaling decoding module 9040. A description will be given of operationof each module of the apparatus for receiving broadcast signals.

The synchronization & demodulation module 9000 can receive input signalsthrough m Rx antennas, perform signal detection and synchronization withrespect to a system corresponding to the apparatus for receivingbroadcast signals and carry out demodulation corresponding to a reverseprocedure of the procedure performed by the apparatus for transmittingbroadcast signals.

The frame parsing module 9100 can parse input signal frames and extractdata through which a service selected by a user is transmitted. If theapparatus for transmitting broadcast signals performs interleaving, theframe parsing module 9100 can carry out deinterleaving corresponding toa reverse procedure of interleaving. In this case, the positions of asignal and data that need to be extracted can be obtained by decodingdata output from the signaling decoding module 9400 to restorescheduling information generated by the apparatus for transmittingbroadcast signals.

The demapping & decoding module 9200 can convert the input signals intobit domain data and then deinterleave the same as necessary. Thedemapping & decoding module 9200 can perform demapping for mappingapplied for transmission efficiency and correct an error generated on atransmission channel through decoding. In this case, the demapping &decoding module 9200 can obtain transmission parameters necessary fordemapping and decoding by decoding the data output from the signalingdecoding module 9400.

The output processor 9300 can perform reverse procedures of variouscompression/signal processing procedures which are applied by theapparatus for transmitting broadcast signals to improve transmissionefficiency. In this case, the output processor 9300 can acquirenecessary control information from data output from the signalingdecoding module 9400. The output of the output processor 8300corresponds to a signal input to the apparatus for transmittingbroadcast signals and may be MPEG-TSs, IP streams (v4 or v6) and genericstreams.

The signaling decoding module 9400 can obtain PLS information from thesignal demodulated by the synchronization & demodulation module 9000. Asdescribed above, the frame parsing module 9100, demapping & decodingmodule 9200 and output processor 9300 can execute functions thereofusing the data output from the signaling decoding module 9400.

FIG. 10 illustrates a frame structure according to an embodiment of thepresent invention.

FIG. 10 shows an example configuration of the frame types and FRUs in asuper-frame. (a) shows a super frame according to an embodiment of thepresent invention, (b) shows FRU (Frame Repetition Unit) according to anembodiment of the present invention, (c) shows frames of variable PHYprofiles in the FRU and (d) shows a structure of a frame.

A super-frame may be composed of eight FRUs. The FRU is a basicmultiplexing unit for TDM of the frames, and is repeated eight times ina super-frame.

Each frame in the FRU belongs to one of the PHY profiles, (base,handheld, advanced) or FEF. The maximum allowed number of the frames inthe FRU is four and a given PHY profile can appear any number of timesfrom zero times to four times in the FRU (e.g., base, base, handheld,advanced). PHY profile definitions can be extended using reserved valuesof the PHY_PROFILE in the preamble, if required.

The FEF part is inserted at the end of the FRU, if included. When theFEF is included in the FRU, the minimum number of FEFs is 8 in asuper-frame. It is not recommended that FEF parts be adjacent to eachother.

One frame is further divided into a number of OFDM symbols and apreamble. As shown in (d), the frame comprises a preamble, one or moreframe signaling symbols (FSS), normal data symbols and a frame edgesymbol (FES).

The preamble is a special symbol that enables fast Futurecast UTB systemsignal detection and provides a set of basic transmission parameters forefficient transmission and reception of the signal. The detaileddescription of the preamble will be will be described later.

The main purpose of the FSS(s) is to carry the PLS data. For fastsynchronization and channel estimation, and hence fast decoding of PLSdata, the FSS has more dense pilot pattern than the normal data symbol.The FES has exactly the same pilots as the FSS, which enablesfrequency-only interpolation within the FES and temporal interpolation,without extrapolation, for symbols immediately preceding the FES.

FIG. 11 illustrates a signaling hierarchy structure of the frameaccording to an embodiment of the present invention.

FIG. 11 illustrates the signaling hierarchy structure, which is splitinto three main parts: the preamble signaling data 11000, the PLS1 data11010 and the PLS2 data 11020. The purpose of the preamble, which iscarried by the preamble symbol in every frame, is to indicate thetransmission type and basic transmission parameters of that frame. ThePLS1 enables the receiver to access and decode the PLS2 data, whichcontains the parameters to access the DP of interest. The PLS2 iscarried in every frame and split into two main parts: PLS2-STAT data andPLS2-DYN data. The static and dynamic portion of PLS2 data is followedby padding, if necessary.

FIG. 12 illustrates preamble signaling data according to an embodimentof the present invention.

Preamble signaling data carries 21 bits of information that are neededto enable the receiver to access PLS data and trace DPs within the framestructure. Details of the preamble signaling data are as follows:

PHY_PROFILE: This 3-bit field indicates the PHY profile type of thecurrent frame. The mapping of different PHY profile types is given inbelow table 5.

TABLE 5 Value PHY profile 000 Base profile 001 Handheld profile 010Advanced profiled 011~110 Reserved 111 FEF

FFT_SIZE: This 2 bit field indicates the FFT size of the current framewithin a frame-group, as described in below table 6.

TABLE 6 Value FFT size 00 8K FFT 01 16K FFT 10 32K FFT 11 Reserved

GI_FRACTION: This 3 bit field indicates the guard interval fractionvalue in the current super-frame, as described in below table 7.

TABLE 7 Value GI_FRACTION 000 1/5 001 1/10 010 1/20 011 1/40 100 1/80101 1/160 110~111 Reserved

EAC_FLAG: This 1 bit field indicates whether the EAC is provided in thecurrent frame. If this field is set to ‘1’, emergency alert service(EAS) is provided in the current frame. If this field set to ‘0’, EAS isnot carried in the current frame. This field can be switched dynamicallywithin a super-frame.

PILOT_MODE: This 1-bit field indicates whether the pilot mode is mobilemode or fixed mode for the current frame in the current frame-group. Ifthis field is set to ‘0’, mobile pilot mode is used. If the field is setto ‘1’, the fixed pilot mode is used.

PAPR_FLAG: This 1-bit field indicates whether PAPR reduction is used forthe current frame in the current frame-group. If this field is set tovalue ‘1’, tone reservation is used for PAPR reduction. If this field isset to ‘0’, PAPR reduction is not used.

FRU_CONFIGURE: This 3-bit field indicates the PHY profile typeconfigurations of the frame repetition units (FRU) that are present inthe current super-frame. All profile types conveyed in the currentsuper-frame are identified in this field in all preambles in the currentsuper-frame. The 3-bit field has a different definition for eachprofile, as show in below table 8.

TABLE 8 Current Current Current Current PHY_PROFILE = PHY_PROFILE =PHY_PROFILE = PHY_PROFILE = ‘000’ (base) ‘001’ (handheld) ‘010’(advanced) ‘111’ (FEF) FRU_CONFIGURE = Only base Only handheld Onlyadvanced Only FEF 000 profile profile present profile present presentpresent FRU_CONFIGURE = Handheld Base profile Base profile Base profile1XX profile present present present present FRU_CONFIGURE = AdvancedAdvanced Handheld Handheld X1X profile profile profile profile presentpresent present present FRU_CONFIGURE = FEF FEF FEF Advanced XX1 presentpresent present profile present

RESERVED: This 7-bit field is reserved for future use.

FIG. 13 illustrates PLS1 data according to an embodiment of the presentinvention.

PLS1 data provides basic transmission parameters including parametersrequired to enable the reception and decoding of the PLS2. As abovementioned, the PLS1 data remain unchanged for the entire duration of oneframe-group. The detailed definition of the signaling fields of the PLS1data are as follows:

PREAMBLE_DATA: This 20-bit field is a copy of the preamble signalingdata excluding the EAC_FLAG.

NUM_FRAME_FRU: This 2-bit field indicates the number of the frames perFRU.

PAYLOAD_TYPE: This 3-bit field indicates the format of the payload datacarried in the frame-group. PAYLOAD_TYPE is signaled as shown in table9.

TABLE 9 value Payload type 1XX TS stream is transmitted X1X IP stream istransmitted XX1 GS stream is transmitted

NUM_FSS: This 2-bit field indicates the number of FSS symbols in thecurrent frame.

SYSTEM_VERSION: This 8-bit field indicates the version of thetransmitted signal format. The SYSTEM_VERSION is divided into two 4-bitfields, which are a major version and a minor version.

Major version: The MSB four bits of SYSTEM_VERSION field indicate majorversion information. A change in the major version field indicates anon-backward-compatible change. The default value is ‘0000’. For theversion described in this standard, the value is set to ‘0000’.

Minor version: The LSB four bits of SYSTEM_VERSION field indicate minorversion information. A change in the minor version field isbackward-compatible.

CELL_ID: This is a 16-bit field which uniquely identifies a geographiccell in an ATSC network. An ATSC cell coverage area may consist of oneor more frequencies, depending on the number of frequencies used perFuturecast UTB system. If the value of the CELL_ID is not known orunspecified, this field is set to ‘0’.

NETWORK_ID: This is a 16-bit field which uniquely identifies the currentATSC network.

SYSTEM_ID: This 16-bit field uniquely identifies the Futurecast UTBsystem within the ATSC network. The Futurecast UTB system is theterrestrial broadcast system whose input is one or more input streams(TS, IP, GS) and whose output is an RF signal. The Futurecast UTB systemcarries one or more PHY profiles and FEF, if any. The same FuturecastUTB system may carry different input streams and use different RFfrequencies in different geographical areas, allowing local serviceinsertion. The frame structure and scheduling is controlled in one placeand is identical for all transmissions within a Futurecast UTB system.One or more Futurecast UTB systems may have the same SYSTEM_ID meaningthat they all have the same physical layer structure and configuration.

The following loop consists of FRU_PHY_PROFILE, FRU_FRAME_LENGTH,FRU_GI_FRACTION, and RESERVED which are used to indicate the FRUconfiguration and the length of each frame type. The loop size is fixedso that four PHY profiles (including a FEF) are signaled within the FRU.If NUM_FRAME_FRU is less than 4, the unused fields are filled withzeros.

FRU_PHY_PROFILE: This 3-bit field indicates the PHY profile type of the(i+1)^(th) (i is the loop index) frame of the associated FRU. This fielduses the same signaling format as shown in the table 8.

FRU_FRAME_LENGTH: This 2-bit field indicates the length of the(i+1)^(th) frame of the associated FRU. Using FRU_FRAME_LENGTH togetherwith FRU_GI_FRACTION, the exact value of the frame duration can beobtained.

FRU_GI_FRACTION: This 3-bit field indicates the guard interval fractionvalue of the (i+1)^(th) frame of the associated FRU. FRU_GI_FRACTION issignaled according to the table 7.

RESERVED: This 4-bit field is reserved for future use.

The following fields provide parameters for decoding the PLS2 data.

PLS2_FEC_TYPE: This 2-bit field indicates the FEC type used by the PLS2protection. The FEC type is signaled according to table 10. The detailsof the LDPC codes will be described later.

TABLE 10 Content PLS2 FEC type 00 4K-1/4 and 7K-3/10 LDPC codes 01~11Reserved

PLS2_MOD: This 3-bit field indicates the modulation type used by thePLS2. The modulation type is signaled according to table 11.

TABLE 11 Value PLS2_MODE 000 BPSK 001 QPSK 010 QAM-16 011 NUQ-64 100~111Reserved

PLS2_SIZE_CELL: This 15-bit field indicates C_(total) _(_) _(partial)_(_) _(block), the size (specified as the number of QAM cells) of thecollection of full coded blocks for PLS2 that is carried in the currentframe-group. This value is constant during the entire duration of thecurrent frame-group.

PLS2_STAT_SIZE_BIT: This 14-bit field indicates the size, in bits, ofthe PLS2-STAT for the current frame-group. This value is constant duringthe entire duration of the current frame-group.

PLS2_DYN_SIZE_BIT: This 14-bit field indicates the size, in bits, of thePLS2-DYN for the current frame-group. This value is constant during theentire duration of the current frame-group.

PLS2_REP_FLAG: This 1-bit flag indicates whether the PLS2 repetitionmode is used in the current frame-group. When this field is set to value‘1’, the PLS2 repetition mode is activated. When this field is set tovalue ‘0’, the PLS2 repetition mode is deactivated.

PLS2_REP_SIZE_CELL: This 15-bit field indicates C_(total) _(_)_(partial) _(_) _(block), the size (specified as the number of QAMcells) of the collection of partial coded blocks for PLS2 carried inevery frame of the current frame-group, when PLS2 repetition is used. Ifrepetition is not used, the value of this field is equal to 0. Thisvalue is constant during the entire duration of the current frame-group.

PLS2_NEXT_FEC_TYPE: This 2-bit field indicates the FEC type used forPLS2 that is carried in every frame of the next frame-group. The FECtype is signaled according to the table 10.

PLS2_NEXT_MOD: This 3-bit field indicates the modulation type used forPLS2 that is carried in every frame of the next frame-group. Themodulation type is signaled according to the table 11.

PLS2_NEXT_REP_FLAG: This 1-bit flag indicates whether the PLS2repetition mode is used in the next frame-group. When this field is setto value ‘1’, the PLS2 repetition mode is activated. When this field isset to value ‘0’, the PLS2 repetition mode is deactivated.

PLS2_NEXT_REP_SIZE_CELL: This 15-bit field indicates C_(total) _(_)_(full) _(_) _(block), The size (specified as the number of QAM cells)of the collection of full coded blocks for PLS2 that is carried in everyframe of the next frame-group, when PLS2 repetition is used. Ifrepetition is not used in the next frame-group, the value of this fieldis equal to 0. This value is constant during the entire duration of thecurrent frame-group.

PLS2_NEXT_REP_STAT_SIZE_BIT: This 14-bit field indicates the size, inbits, of the PLS2-STAT for the next frame-group. This value is constantin the current frame-group.

PLS2_NEXT_REP_DYN_SIZE_BIT: This 14-bit field indicates the size, inbits, of the PLS2-DYN for the next frame-group. This value is constantin the current frame-group.

PLS2_AP_MODE: This 2-bit field indicates whether additional parity isprovided for PLS2 in the current frame-group. This value is constantduring the entire duration of the current frame-group. The below table12 gives the values of this field. When this field is set to ‘00’,additional parity is not used for the PLS2 in the current frame-group.

TABLE 12 Value PLS2-AP mode 00 AP is not provided 01 AP1 mode 10~11Reserved

PLS2_AP_SIZE_CELL: This 15-bit field indicates the size (specified asthe number of QAM cells) of the additional parity bits of the PLS2. Thisvalue is constant during the entire duration of the current frame-group.

PLS2_NEXT_AP_MODE: This 2-bit field indicates whether additional parityis provided for PLS2 signaling in every frame of next frame-group. Thisvalue is constant during the entire duration of the current frame-group.The table 12 defines the values of this field

PLS2_NEXT_AP_SIZE_CELL: This 15-bit field indicates the size (specifiedas the number of QAM cells) of the additional parity bits of the PLS2 inevery frame of the next frame-group. This value is constant during theentire duration of the current frame-group.

RESERVED: This 32-bit field is reserved for future use.

CRC_32: A 32-bit error detection code, which is applied to the entirePLS1 signaling.

FIG. 14 illustrates PLS2 data according to an embodiment of the presentinvention.

FIG. 14 illustrates PLS2-STAT data of the PLS2 data. The PLS2-STAT dataare the same within a frame-group, while the PLS2-DYN data provideinformation that is specific for the current frame.

The details of fields of the PLS2-STAT data are as follows:

FIC_FLAG: This 1-bit field indicates whether the FIC is used in thecurrent frame-group. If this field is set to ‘1’, the FIC is provided inthe current frame. If this field set to ‘0’, the FIC is not carried inthe current frame. This value is constant during the entire duration ofthe current frame-group.

AUX_FLAG: This 1-bit field indicates whether the auxiliary stream(s) isused in the current frame-group. If this field is set to ‘1’, theauxiliary stream is provided in the current frame. If this field set to‘0’, the auxiliary stream is not carried in the current frame. Thisvalue is constant during the entire duration of current frame-group.

NUM_DP: This 6-bit field indicates the number of DPs carried within thecurrent frame. The value of this field ranges from 1 to 64, and thenumber of DPs is NUM_DP+1.

DP_ID: This 6-bit field identifies uniquely a DP within a PHY profile.

DP_TYPE: This 3-bit field indicates the type of the DP. This is signaledaccording to the below table 13.

TABLE 13 Value DP Type 000 DP Type 1 001 DP Type 2 010~111 reserved

DP_GROUP_ID: This 8-bit field identifies the DP group with which thecurrent DP is associated. This can be used by a receiver to access theDPs of the service components associated with a particular service,which will have the same DP_GROUP_ID.

BASE_DP_ID: This 6-bit field indicates the DP carrying service signalingdata (such as PSI/SI) used in the Management layer. The DP indicated byBASE_DP_ID may be either a normal DP carrying the service signaling dataalong with the service data or a dedicated DP carrying only the servicesignaling data

DP_FEC_TYPE: This 2-bit field indicates the FEC type used by theassociated DP. The FEC type is signaled according to the below table 14.

TABLE 14 Value FEC_TYPE 00 16K LDPC 01 64K LDPC 10~11 Reserved

DP_COD: This 4-bit field indicates the code rate used by the associatedDP. The code rate is signaled according to the below table 15.

TABLE 15 Value Code rate 0000  5/15 0001  6/15 0010  7/15 0011  8/150100  9/15 0101 10/15 0110 11/15 0111 12/15 1000 13/15 1001~1111Reserved

DP_MOD: This 4-bit field indicates the modulation used by the associatedDP. The modulation is signaled according to the below table 16.

TABLE 16 Value Modulation 0000 QPSK 0001 QAM-16 0010 NUQ-64 0011 NUQ-2560100 NUQ-1024 0101 NUC-16 0110 NUC-64 0111 NUC-256 1000 NUC-10241001~1111 reserved

DP_SSD_FLAG: This 1-bit field indicates whether the SSD mode is used inthe associated DP. If this field is set to value ‘1’, SSD is used. Ifthis field is set to value ‘0’, SSD is not used.

The following field appears only if PHY_PROFILE is equal to ‘010’, whichindicates the advanced profile:

DP_MIMO: This 3-bit field indicates which type of MIMO encoding processis applied to the associated DP. The type of MIMO encoding process issignaled according to the table 17.

TABLE 17 Value MIMO encoding 000 FR-SM 001 FRFD-SM 010~111 reserved

DP_TI_TYPE: This 1-bit field indicates the type of time-interleaving. Avalue of ‘0’ indicates that one TI group corresponds to one frame andcontains one or more TI-blocks. A value of ‘1’ indicates that one TIgroup is carried in more than one frame and contains only one TI-block.

DP_TI_LENGTH: The use of this 2-bit field (the allowed values are only1, 2, 4, 8) is determined by the values set within the DP_TI_TYPE fieldas follows:

If the DP_TI_TYPE is set to the value ‘1’, this field indicates P_(I),the number of the frames to which each TI group is mapped, and there isone TI-block per TI group (N_(TI)=1). The allowed P_(I) values with2-bit field are defined in the below table 18.

If the DP_TI_TYPE is set to the value ‘0’, this field indicates thenumber of TI-blocks N_(TI) per TI group, and there is one TI group perframe (P_(I)=1). The allowed P_(I) values with 2-bit field are definedin the below table 18.

TABLE 18 2-bit field P_(l) N_(TI) 00 1 1 01 2 2 10 4 3 11 8 4

DP_FRAME_INTERVAL: This 2-bit field indicates the frame interval(I_(JUMP)) within the frame-group for the associated DP and the allowedvalues are 1, 2, 4, 8 (the corresponding 2-bit field is ‘00’, ‘01’,‘10’, or 11′, respectively). For DPs that do not appear every frame ofthe frame-group, the value of this field is equal to the intervalbetween successive frames. For example, if a DP appears on the frames 1,5, 9, 13, etc., this field is set to ‘4’. For DPs that appear in everyframe, this field is set to ‘1’.

DP_TI_BYPASS: This 1-bit field determines the availability of timeinterleaver 5050. If time interleaving is not used for a DP, it is setto ‘1’. Whereas if time interleaving is used it is set to ‘0’.

DP_FIRST_FRAME_IDX: This 5-bit field indicates the index of the firstframe of the super-frame in which the current DP occurs. The value ofDP_FIRST_FRAME_IDX ranges from 0 to 31

DP_NUM_BLOCK_MAX: This 10-bit field indicates the maximum value ofDP_NUM_BLOCKS for this DP. The value of this field has the same range asDP_NUM_BLOCKS.

DP_PAYLOAD_TYPE: This 2-bit field indicates the type of the payload datacarried by the given DP. DP_PAYLOAD_TYPE is signaled according to thebelow table 19.

TABLE 19 Value Payload Type 00 TS. 01 IP 10 GS 11 reserved

DP_INBAND_MODE: This 2-bit field indicates whether the current DPcarries in-band signaling information. The in-band signaling type issignaled according to the below table 20.

TABLE 20 Value In-band mode 00 In-band signaling is not carried. 01INBAND-PLS is carried only 10 INBAND-ISSY is carried only 11 INBAND-PLSand INBAND-ISSY are carried

DP_PROTOCOL_TYPE: This 2-bit field indicates the protocol type of thepayload carried by the given DP. It is signaled according to the belowtable 21 when input payload types are selected.

TABLE 21 If DP_PAYLOAD_TYPE If DP_PAYLOAD_TYPE If DP_PAYLOAD_TYPE ValueIs TS Is IP Is GS 00 MPEG2-TS IPv4 (Note) 01 Reserved IPv6 Reserved 10Reserved Reserved Reserved 11 Reserved Reserved Reserved

DP_CRC_MODE: This 2-bit field indicates whether CRC encoding is used inthe Input Formatting block. The CRC mode is signaled according to thebelow table 22.

TABLE 22 Value CRC mode 00 Not used 01 CRC-8 10 CRC-16 11 CIRC-32

DNP_MODE: This 2-bit field indicates the null-packet deletion mode usedby the associated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). DNP_MODEis signaled according to the below table 23. If DP_PAYLOAD_TYPE is notTS (‘00’), DNP_MODE is set to the value ‘00’.

TABLE 23 Value Null-packet deletion mode 00 Not used 01 DNP-NORMAL 10DNP-OFFSET 11 reserved

ISSY_MODE: This 2-bit field indicates the ISSY mode used by theassociated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). The ISSY_MODE issignaled according to the below table 24 If DP_PAYLOAD_TYPE is not TS(‘00’), ISSY_MODE is set to the value ‘00’.

TABLE 24 Value ISSY mode 00 Not used 01 ISSY-UP 10 ISSY-BBF 11 reserved

HC_MODE_TS: This 2-bit field indicates the TS header compression modeused by the associated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). TheHC_MODE_TS is signaled according to the below table 25.

TABLE 25 Value Header compression mode 00 HC_MODE_TS 1 01 HC_MODE_TS 210 HC_MODE_TS 3 11 HC_MODE_TS 4

HC_MODE_IP: This 2-bit field indicates the IP header compression modewhen DP_PAYLOAD_TYPE is set to IP (‘01’). The HC_MODE_IP is signaledaccording to the below table 26.

TABLE 26 Value Header compression mode 00 No compression 01 HC_MODE_IP 110~11 reserved

PID: This 13-bit field indicates the PID number for TS headercompression when DP_PAYLOAD_TYPE is set to TS (‘00’) and HC_MODE_TS isset to ‘01’ or ‘10’.

RESERVED: This 8-bit field is reserved for future use.

The following field appears only if FIC_FLAG is equal to ‘1’:

FIC_VERSION: This 8-bit field indicates the version number of the FIC.

FIC_LENGTH_BYTE: This 13-bit field indicates the length, in bytes, ofthe FIC.

RESERVED: This 8-bit field is reserved for future use.

The following field appears only if AUX_FLAG is equal to ‘1’:

NUM_AUX: This 4-bit field indicates the number of auxiliary streams.Zero means no auxiliary streams are used.

AUX_CONFIG_RFU: This 8-bit field is reserved for future use.

AUX_STREAM_TYPE: This 4-bit is reserved for future use for indicatingthe type of the current auxiliary stream.

AUX_PRIVATE_CONFIG: This 28-bit field is reserved for future use forsignaling auxiliary streams.

FIG. 15 illustrates PLS2 data according to another embodiment of thepresent invention.

FIG. 15 illustrates PLS2-DYN data of the PLS2 data. The values of thePLS2-DYN data may change during the duration of one frame-group, whilethe size of fields remains constant.

The details of fields of the PLS2-DYN data are as follows:

FRAME_INDEX: This 5-bit field indicates the frame index of the currentframe within the super-frame. The index of the first frame of thesuper-frame is set to ‘0’.

PLS_CHANGE_COUNTER: This 4-bit field indicates the number ofsuper-frames ahead where the configuration will change. The nextsuper-frame with changes in the configuration is indicated by the valuesignaled within this field. If this field is set to the value ‘0000’, itmeans that no scheduled change is foreseen: e.g., value ‘1’ indicatesthat there is a change in the next super-frame.

FIC_CHANGE_COUNTER: This 4-bit field indicates the number ofsuper-frames ahead where the configuration (i.e., the contents of theFIC) will change. The next super-frame with changes in the configurationis indicated by the value signaled within this field. If this field isset to the value ‘0000’, it means that no scheduled change is foreseen:e.g. value ‘0001’ indicates that there is a change in the nextsuper-frame.

RESERVED: This 16-bit field is reserved for future use.

The following fields appear in the loop over NUM_DP, which describe theparameters associated with the DP carried in the current frame.

(a) DP_ID: This 6-bit field indicates uniquely the DP within a PHYprofile.

DP_START: This 15-bit (or 13-bit) field indicates the start position ofthe first of the DPs using the DPU addressing scheme. The DP_START fieldhas differing length according to the PHY profile and FFT size as shownin the below table 27.

TABLE 27 DP_START field size PHY profile 64K 16K Base 13 bit 15 bitHandheld — 13 bit Advanced 13 bit 15 bit

DP_NUM_BLOCK: This 10-bit field indicates the number of FEC blocks inthe current TI group for the current DP. The value of DP_NUM_BLOCKranges from 0 to 1023

(b) RESERVED: This 8-bit field is reserved for future use.

The following fields indicate the FIC parameters associated with theEAC.

EAC_FLAG: This 1-bit field indicates the existence of the EAC in thecurrent frame. This bit is the same value as the EAC_FLAG in thepreamble.

EAS_WAKE_UP_VERSION_NUM: This 8-bit field indicates the version numberof a wake-up indication.

If the EAC_FLAG field is equal to ‘1’, the following 12 bits areallocated for EAC_LENGTH_BYTE field. If the EAC_FLAG field is equal to‘0’, the following 12 bits are allocated for EAC_COUNTER.

EAC_LENGTH_BYTE: This 12-bit field indicates the length, in byte, of theEAC.

EAC_COUNTER: This 12-bit field indicates the number of the frames beforethe frame where the EAC arrives.

The following field appears only if the AUX_FLAG field is equal to ‘1’:

(c) AUX_PRIVATE_DYN: This 48-bit field is reserved for future use forsignaling auxiliary streams. The meaning of this field depends on thevalue of AUX_STREAM_TYPE in the configurable PLS2-STAT.

CRC_32: A 32-bit error detection code, which is applied to the entirePLS2.

FIG. 16 illustrates a logical structure of a frame according to anembodiment of the present invention.

As above mentioned, the PLS, EAC, FIC, DPs, auxiliary streams and dummycells are mapped into the active carriers of the OFDM symbols in theframe. The PLS1 and PLS2 are first mapped into one or more FSS(s). Afterthat, EAC cells, if any, are mapped immediately following the PLS field,followed next by FIC cells, if any. The DPs are mapped next after thePLS or EAC, FIC, if any. Type 1 DPs follows first, and Type 2 DPs next.The details of a type of the DP will be described later. In some case,DPs may carry some special data for EAS or service signaling data. Theauxiliary stream or streams, if any, follow the DPs, which in turn arefollowed by dummy cells. Mapping them all together in the abovementioned order, i.e. PLS, EAC, FIC, DPs, auxiliary streams and dummydata cells exactly fill the cell capacity in the frame.

FIG. 17 illustrates PLS mapping according to an embodiment of thepresent invention.

PLS cells are mapped to the active carriers of FSS(s). Depending on thenumber of cells occupied by PLS, one or more symbols are designated asFSS(s), and the number of FSS(s) N_(FSS) is signaled by NUM_FSS in PLS1.The FSS is a special symbol for carrying PLS cells. Since robustness andlatency are critical issues in the PLS, the FSS(s) has higher density ofpilots allowing fast synchronization and frequency-only interpolationwithin the FSS.

PLS cells are mapped to active carriers of the N_(FSS) FSS(s) in atop-down manner as shown in an example in FIG. 17. The PLS1 cells aremapped first from the first cell of the first FSS in an increasing orderof the cell index. The PLS2 cells follow immediately after the last cellof the PLS1 and mapping continues downward until the last cell index ofthe first FSS. If the total number of required PLS cells exceeds thenumber of active carriers of one FSS, mapping proceeds to the next FSSand continues in exactly the same manner as the first FSS.

After PLS mapping is completed, DPs are carried next. If EAC, FIC orboth are present in the current frame, they are placed between PLS and“normal” DPs.

FIG. 18 illustrates EAC mapping according to an embodiment of thepresent invention.

EAC is a dedicated channel for carrying EAS messages and links to theDPs for EAS. EAS support is provided but EAC itself may or may not bepresent in every frame. EAC, if any, is mapped immediately after thePLS2 cells. EAC is not preceded by any of the FIC, DPs, auxiliarystreams or dummy cells other than the PLS cells. The procedure ofmapping the EAC cells is exactly the same as that of the PLS.

The EAC cells are mapped from the next cell of the PLS2 in increasingorder of the cell index as shown in the example in FIG. 18. Depending onthe EAS message size, EAC cells may occupy a few symbols, as shown inFIG. 18.

EAC cells follow immediately after the last cell of the PLS2, andmapping continues downward until the last cell index of the last FSS. Ifthe total number of required EAC cells exceeds the number of remainingactive carriers of the last FSS mapping proceeds to the next symbol andcontinues in exactly the same manner as FSS(s). The next symbol formapping in this case is the normal data symbol, which has more activecarriers than a FSS.

After EAC mapping is completed, the FIC is carried next, if any exists.If FIC is not transmitted (as signaled in the PLS2 field), DPs followimmediately after the last cell of the EAC.

FIG. 19 illustrates FIC mapping according to an embodiment of thepresent invention.

(d) shows an example mapping of FIC cell without EAC and (b) shows anexample mapping of FIC cell with EAC.

FIC is a dedicated channel for carrying cross-layer information toenable fast service acquisition and channel scanning. This informationprimarily includes channel binding information between DPs and theservices of each broadcaster. For fast scan, a receiver can decode FICand obtain information such as broadcaster ID, number of services, andBASE_DP_ID. For fast service acquisition, in addition to FIC, base DPcan be decoded using BASE_DP_ID. Other than the content it carries, abase DP is encoded and mapped to a frame in exactly the same way as anormal DP. Therefore, no additional description is required for a baseDP. The FIC data is generated and consumed in the Management Layer. Thecontent of FIC data is as described in the Management Layerspecification.

The FIC data is optional and the use of FIC is signaled by the FIC_FLAGparameter in the static part of the PLS2. If FIC is used, FIC_FLAG isset to ‘1’ and the signaling field for FIC is defined in the static partof PLS2. Signaled in this field are FIC_VERSION, and FIC_LENGTH_BYTE.FIC uses the same modulation, coding and time interleaving parameters asPLS2. FIC shares the same signaling parameters such as PLS2_MOD and PLS2FEC. FIC data, if any, is mapped immediately after PLS2 or EAC if any.FIC is not preceded by any normal DPs, auxiliary streams or dummy cells.The method of mapping FIC cells is exactly the same as that of EAC whichis again the same as PLS.

Without EAC after PLS, FIC cells are mapped from the next cell of thePLS2 in an increasing order of the cell index as shown in an example in(a). Depending on the FIC data size, FIC cells may be mapped over a fewsymbols, as shown in (b).

FIC cells follow immediately after the last cell of the PLS2, andmapping continues downward until the last cell index of the last FSS. Ifthe total number of required FIC cells exceeds the number of remainingactive carriers of the last FSS, mapping proceeds to the next symbol andcontinues in exactly the same manner as FSS(s). The next symbol formapping in this case is the normal data symbol which has more activecarriers than a FSS.

If EAS messages are transmitted in the current frame, EAC precedes FIC,and FIC cells are mapped from the next cell of the EAC in an increasingorder of the cell index as shown in (b).

After FIC mapping is completed, one or more DPs are mapped, followed byauxiliary streams, if any, and dummy cells.

FIG. 20 illustrates a type of DP according to an embodiment of thepresent invention.

(e) shows type 1 DP and (b) shows type 2 DP.

After the preceding channels, i.e., PLS, EAC and FIC, are mapped, cellsof the DPs are mapped. A DP is categorized into one of two typesaccording to mapping method:

Type 1 DP: DP is mapped by TDM

Type 2 DP: DP is mapped by FDM

The type of DP is indicated by DP_TYPE field in the static part of PLS2.FIG. 20 illustrates the mapping orders of Type 1 DPs and Type 2 DPs.Type 1 DPs are first mapped in the increasing order of cell index, andthen after reaching the last cell index, the symbol index is increasedby one. Within the next symbol, the DP continues to be mapped in theincreasing order of cell index starting from p=0. With a number of DPsmapped together in one frame, each of the Type 1 DPs are grouped intime, similar to TDM multiplexing of DPs.

Type 2 DPs are first mapped in the increasing order of symbol index, andthen after reaching the last OFDM symbol of the frame, the cell indexincreases by one and the symbol index rolls back to the first availablesymbol and then increases from that symbol index. After mapping a numberof DPs together in one frame, each of the Type 2 DPs are grouped infrequency together, similar to FDM multiplexing of DPs.

Type 1 DPs and Type 2 DPs can coexist in a frame if needed with onerestriction; Type 1 DPs always precede Type 2 DPs. The total number ofOFDM cells carrying Type 1 and Type 2 DPs cannot exceed the total numberof OFDM cells available for transmission of DPs:D _(DP1) +D _(DP2) ≦D _(DP)  [Expression 2]

where D_(DP1) is the number of OFDM cells occupied by Type 1 DPs,D_(DP2) is the number of cells occupied by Type 2 DPs. Since PLS, EAC,FIC are all mapped in the same way as Type 1 DP, they all follow “Type 1mapping rule”. Hence, overall, Type 1 mapping always precedes Type 2mapping.

FIG. 21 illustrates DP mapping according to an embodiment of the presentinvention.

(f) shows an addressing of OFDM cells for mapping type 1 DPs and (b)shows an addressing of OFDM cells for mapping for type 2 DPs.

Addressing of OFDM cells for mapping Type 1 DPs (0, . . . , D_(DP1)−1)is defined for the active data cells of Type 1 DPs. The addressingscheme defines the order in which the cells from the TIs for each of theType 1 DPs are allocated to the active data cells. It is also used tosignal the locations of the DPs in the dynamic part of the PLS2.

Without EAC and FIC, address 0 refers to the cell immediately followingthe last cell carrying PLS in the last FSS. If EAC is transmitted andFIC is not in the corresponding frame, address 0 refers to the cellimmediately following the last cell carrying EAC. If FIC is transmittedin the corresponding frame, address 0 refers to the cell immediatelyfollowing the last cell carrying FIC. Address 0 for Type 1 DPs can becalculated considering two different cases as shown in (a). In theexample in (a), PLS, EAC and FIC are assumed to be all transmitted.Extension to the cases where either or both of EAC and FIC are omittedis straightforward. If there are remaining cells in the FSS aftermapping all the cells up to FIC as shown on the left side of (a).

Addressing of OFDM cells for mapping Type 2 DPs (0, . . . , D_(DP2)−1)is defined for the active data cells of Type 2 DPs. The addressingscheme defines the order in which the cells from the TIs for each of theType 2 DPs are allocated to the active data cells. It is also used tosignal the locations of the DPs in the dynamic part of the PLS2.

Three slightly different cases are possible as shown in (b). For thefirst case shown on the left side of (b), cells in the last FSS areavailable for Type 2 DP mapping. For the second case shown in themiddle, FIC occupies cells of a normal symbol, but the number of FICcells on that symbol is not larger than C_(FSS). The third case, shownon the right side in (b), is the same as the second case except that thenumber of FIC cells mapped on that symbol exceeds C_(FSS).

The extension to the case where Type 1 DP(s) precede Type 2 DP(s) isstraightforward since PLS, EAC and FIC follow the same “Type 1 mappingrule” as the Type 1 DP(s).

A data pipe unit (DPU) is a basic unit for allocating data cells to a DPin a frame.

A DPU is defined as a signaling unit for locating DPs in a frame. A CellMapper 7010 may map the cells produced by the TIs for each of the DPs. ATime interleaver 5050 outputs a series of TI-blocks and each TI-blockcomprises a variable number of XFECBLOCKs which is in turn composed of aset of cells. The number of cells in an XFECBLOCK, N_(cells), isdependent on the FECBLOCK size, N_(ldpc), and the number of transmittedbits per constellation symbol. A DPU is defined as the greatest commondivisor of all possible values of the number of cells in a XFECBLOCK,N_(cells), supported in a given PHY profile. The length of a DPU incells is defined as L_(DPU). Since each PHY profile supports differentcombinations of FECBLOCK size and a different number of bits perconstellation symbol, L_(DPU) is defined on a PHY profile basis.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention before bit interleaving. As above mentioned, Data FECencoder may perform the FEC encoding on the input BBF to generateFECBLOCK procedure using outer coding (BCH), and inner coding (LDPC).The illustrated FEC structure corresponds to the FECBLOCK. Also, theFECBLOCK and the FEC structure have same value corresponding to a lengthof LDPC codeword.

The BCH encoding is applied to each BBF (K_(bch) bits), and then LDPCencoding is applied to BCH-encoded BBF (K_(ldpc) bits=N_(bch) bits) asillustrated in FIG. 22.

The value of N_(ldpc) is either 64800 bits (long FECBLOCK) or 16200 bits(short FECBLOCK).

The below table 28 and table 29 show FEC encoding parameters for a longFECBLOCK and a short FECBLOCK, respectively.

TABLE 28 BCH error LDPC correction Rate N_(ldpc) K_(ldpc) K_(bch)capability N_(bch)-K_(bch)  5/15 64800 21600 21408 12 192  6/15 2592025728  7/15 30240 30048  8/15 34560 34368  9/15 38880 38688 10/15 4320043008 11/15 47520 47328 12/15 51840 51648 13/15 56160 55968

TABLE 29 BCH error LDPC correction Rate N_(ldpc) K_(ldpc) K_(bch)capability N_(bch)- K_(bch)  5/15 16200 5400 5232 12 168  6/15 6480 6312 7/15 7560 7392  8/15 8640 8472  9/15 9720 9552 10/15 10800 10632 11/1511880 11712 12/15 12960 12792 13/15 14040 13872

The details of operations of the BCH encoding and LDPC encoding are asfollows:

A 12-error correcting BCH code is used for outer encoding of the BBF.The BCH generator polynomial for short FECBLOCK and long FECBLOCK areobtained by multiplying together all polynomials.

LDPC code is used to encode the output of the outer BCH encoding. Togenerate a completed B_(ldpc) (FECBLOCK), P_(ldpc) (parity bits) isencoded systematically from each I_(ldpc) (BCH-encoded BBF), andappended to I_(ldpc). The completed B_(ldpc) (FECBLOCK) are expressed asfollow Expression.B _(ldpc) =[I _(ldpc) P _(ldpc) ]=[i ₀ ,i ₁ , . . . ,i _(K) _(ldpc) ₋₁,p ₀ ,p ₁ , . . . ,p _(N) _(ldpc) _(-K) _(ldpc) ₋₁]  [Expression 3]

The parameters for long FECBLOCK and short FECBLOCK are given in theabove table 28 and 29, respectively.

The detailed procedure to calculate N_(ldpc)−K_(ldpc) parity bits forlong FECBLOCK, is as follows:

1) Initialize the parity bits,p ₀ =p ₁ =p ₂ = . . . =p _(N) _(ldpc) _(-K) _(ldpc) ₋₁=0  [Expression 4]

2) Accumulate the first information bit—i₀, at parity bit addressesspecified in the first row of an addresses of parity check matrix. Thedetails of addresses of parity check matrix will be described later. Forexample, for rate 13/15:

$\begin{matrix}{{p_{983} = {p_{983} \oplus i_{0}}}{p_{2815} = {p_{2815} \oplus i_{0}}}{p_{4837} = {p_{4837} \oplus i_{0}}}{p_{4989} = {p_{4989} \oplus i_{0}}}{p_{6138} = {p_{6138} \oplus i_{0}}}{p_{6458} = {p_{6458} \oplus i_{0}}}{p_{6921} = {p_{6921} \oplus i_{0}}}{p_{6974} = {p_{6974} \oplus i_{0}}}{p_{7572} = {p_{7572} \oplus i_{0}}}{p_{8260} = {p_{8260} \oplus i_{0}}}{p_{8496} = {p_{8496} \oplus i_{0}}}} & \left\lbrack {{Expression}\mspace{14mu} 5} \right\rbrack\end{matrix}$

3) For the next 359 information bits, i_(s), s=1, 2, . . . , 359accumulate i_(s) at parity bit addresses using following Expression.{x+(s mod 360)×Q _(ldpc)} mod(N _(ldpc) −K _(ldpc))  [Expression 6]

where x denotes the address of the parity bit accumulator correspondingto the first bit i₀, and Q_(ldpc) is a code rate dependent constantspecified in the addresses of parity check matrix. Continuing with theexample, Q_(ldpc)=24 for rate 13/15, so for information bit i₁, thefollowing operations are performed:

$\begin{matrix}{{p_{1007} = {p_{1007} \oplus i_{i}}}{p_{2839} = {p_{2839} \oplus i_{i}}}{p_{4861} = {p_{4861} \oplus i_{i}}}{p_{5013} = {p_{5013} \oplus i_{i}}}{p_{6162} = {p_{6162} \oplus i_{i}}}{p_{6482} = {p_{6482} \oplus i_{i}}}{p_{6945} = {p_{6945} \oplus i_{i}}}{p_{6998} = {p_{6998} \oplus i_{i}}}{p_{7596} = {p_{7596} \oplus i_{i}}}{p_{8284} = {p_{8284} \oplus i_{i}}}{p_{8520} = {p_{8520} \oplus i_{i}}}} & \left\lbrack {{Expression}\mspace{14mu} 7} \right\rbrack\end{matrix}$

4) For the 361st information bit i₃₆₀, the addresses of the parity bitaccumulators are given in the second row of the addresses of paritycheck matrix. In a similar manner the addresses of the parity bitaccumulators for the following 359 information bits i_(s), s=361, 362, .. . , 719 are obtained using the Expression 6, where x denotes theaddress of the parity bit accumulator corresponding to the informationbit i₃₆₀, i.e., the entries in the second row of the addresses of paritycheck matrix.

5) In a similar manner, for every group of 360 new information bits, anew row from addresses of parity check matrixes used to find theaddresses of the parity bit accumulators.

After all of the information bits are exhausted, the final parity bitsare obtained as follows:

6) Sequentially perform the following operations starting with i=1p _(i) =p⊕p _(i-1) , i=1,2, . . . , N _(ldpc) −K _(ldpc)−1  [Expression8]

where final content of p_(i), i=0, 1, . . . N_(ldpc)−K_(ldpc)−1 is equalto the parity bit p_(i).

TABLE 30 Code Rate O_(ldpc)  5/15 120  6/15 108  7/15 96  8/15 84  9/1572 10/15 60 11/15 48 12/15 36 13/15 24

This LDPC encoding procedure for a short FECBLOCK is in accordance witht LDPC encoding procedure for the long FECBLOCK, except replacing thetable 30 with table 31, and replacing the addresses of parity checkmatrix for the long FECBLOCK with the addresses of parity check matrixfor the short FECBLOCK.

TABLE 31 Code Rate O_(ldpc)  5/15 30  6/15 27  7/15 24  8/15 21  9/15 1810/15 15 11/15 12 12/15 9 13/15 6

FIG. 23 illustrates a bit interleaving according to an embodiment of thepresent invention.

The outputs of the LDPC encoder are bit-interleaved, which consists ofparity interleaving followed by Quasi-Cyclic Block (QCB) interleavingand inner-group interleaving.

(g) shows Quasi-Cyclic Block (QCB) interleaving and (b) showsinner-group interleaving.

The FECBLOCK may be parity interleaved. At the output of the parityinterleaving, the LDPC codeword consists of 180 adjacent QC blocks in along FECBLOCK and 45 adjacent QC blocks in a short FECBLOCK. Each QCblock in either a long or short FECBLOCK consists of 360 bits. Theparity interleaved LDPC codeword is interleaved by QCB interleaving. Theunit of QCB interleaving is a QC block. The QC blocks at the output ofparity interleaving are permutated by QCB interleaving as illustrated inFIG. 23, where N_(cells)=64800/η_(mod) or 16200/η_(mod) according to theFECBLOCK length. The QCB interleaving pattern is unique to eachcombination of modulation type and LDPC code rate.

After QCB interleaving, inner-group interleaving is performed accordingto modulation type and order (η_(mod)) which is defined in the belowtable 32. The number of QC blocks for one inner-group, N_(QCB) _(_)_(IG), is also defined.

TABLE 32 Modulation type η_(mod) N_(QCB)_IG QAM-16 4 2 NUC-16 4 4 NUQ-646 3 NUC-64 6 6 NUQ-256 8 4 NUC-256 8 8 NUQ-1024 10 5 NUC-1024 10 10

The inner-group interleaving process is performed with N_(QCB) _(_)_(IG) QC blocks of the QCB interleaving output. Inner-group interleavinghas a process of writing and reading the bits of the inner-group using360 columns and N_(QCB) _(_) _(IG) rows. In the write operation, thebits from the QCB interleaving output are written row-wise. The readoperation is performed column-wise to read out m bits from each row,where m is equal to 1 for NUC and 2 for NUQ.

FIG. 24 illustrates a cell-word demultiplexing according to anembodiment of the present invention.

(h) shows a cell-word demultiplexing for 8 and 12 bpcu MIMO and (b)shows a cell-word demultiplexing for 10 bpcu MIMO.

Each cell word (c_(0,l), c_(1,l), . . . , c_(ηmod-1,l)) of the bitinterleaving output is demultiplexed into (d_(1,0,m), d_(1,1,m) . . . ,d_(1,ηmod-1,m)) and (d_(2,0,m), d_(2,1,m) . . . , d_(2,ηmod-1,m)) asshown in (a), which describes the cell-word demultiplexing process forone XFECBLOCK.

For the 10 bpcu MIMO case using different types of NUQ for MIMOencoding, the Bit Interleaver for NUQ-1024 is re-used. Each cell word(c_(0,l), c_(1,l), . . . , c_(9,l)) of the Bit Interleaver output isdemultiplexed into (d_(1,0,m), d_(1,1,m) . . . , d_(1,3,m)) and(d_(2,0,m), d_(2,1,m) . . . , d_(2,5,m)), as shown in (b).

FIG. 25 illustrates a time interleaving according to an embodiment ofthe present invention.

(i) to (c) show examples of TI mode.

The time interleaver operates at the DP level. The parameters of timeinterleaving (TI) may be set differently for each DP.

The following parameters, which appear in part of the PLS2-STAT data,configure the TI:

DP_TI_TYPE (allowed values: 0 or 1): Represents the TI mode; ‘0’indicates the mode with multiple TI blocks (more than one TI block) perTI group. In this case, one TI group is directly mapped to one frame (nointer-frame interleaving). ‘1’ indicates the mode with only one TI blockper TI group. In this case, the TI block may be spread over more thanone frame (inter-frame interleaving).

DP_TI_LENGTH: If DP_TI_TYPE=‘0’, this parameter is the number of TIblocks N_(TI) per TI group. For DP_TI_TYPE=‘1’, this parameter is thenumber of frames P_(I) spread from one TI group.

DP_NUM_BLOCK_MAX (allowed values: 0 to 1023): Represents the maximumnumber of XFECBLOCKs per TI group.

DP_FRAME_INTERVAL (allowed values: 1, 2, 4, 8): Represents the number ofthe frames I_(JUMP) between two successive frames carrying the same DPof a given PHY profile.

DP_TI_BYPASS (allowed values: 0 or 1): If time interleaving is not usedfor a DP, this parameter is set to ‘1’. It is set to ‘0’ if timeinterleaving is used.

Additionally, the parameter DP_NUM_BLOCK from the PLS2-DYN data is usedto represent the number of XFECBLOCKs carried by one TI group of the DP.

When time interleaving is not used for a DP, the following TI group,time interleaving operation, and TI mode are not considered. However,the Delay Compensation block for the dynamic configuration informationfrom the scheduler will still be required. In each DP, the XFECBLOCKsreceived from the SSD/MIMO encoding are grouped into TI groups. That is,each TI group is a set of an integer number of XFECBLOCKs and willcontain a dynamically variable number of XFECBLOCKs. The number ofXFECBLOCKs in the TI group of index n is denoted by N_(xBLOCK) _(_)_(Group)(n) and is signaled as DP_NUM_BLOCK in the PLS2-DYN data. Notethat N_(xBLOCK) _(_) _(Group)(n) may vary from the minimum value of 0 tothe maximum value N_(xBLOCK) _(_) _(Group) _(_) _(MAX) (corresponding toDP_NUM_BLOCK_MAX) of which the largest value is 1023.

Each TI group is either mapped directly onto one frame or spread overP_(I) frames. Each TI group is also divided into more than one TI blocks(N_(TI)), where each TI block corresponds to one usage of timeinterleaver memory. The TI blocks within the TI group may containslightly different numbers of XFECBLOCKs. If the TI group is dividedinto multiple TI blocks, it is directly mapped to only one frame. Thereare three options for time interleaving (except the extra option ofskipping the time interleaving) as shown in the below table 33.

TABLE 33 Modes Descriptions Option- Each TI group contains one TI blockand is mapped directly to 1 one frame as shown in (a). This option issignaled in the PLS2- STAT by DP_TI_TYPE=‘0’ and DP_TI_LENGTH = ‘1’(N_(TI) = 1). Option- Each TI group contains one TI block and is mappedto more 2 than one frame. (b) shows an example, where one TI group ismapped to two frames, i.e., DP_TI_LENGTH = ‘2’ (P_(I) = 2) andDP_FRAME_INTERVAL (I_(JUMP) = 2). This provides greater time diversityfor low data-rate services. This option is signaled in the PLS2-STAT byDP_TI_TYPE = ‘1’. Option- Each TI group is divided into multiple TIblocks and is mapped 3 directly to one frame as shown in (c). Each TIblock may use full TI memory, so as to provide the maximum bit-rate fora DP. This option is signaled in the PLS2-STAT signaling byDP_TI_TYPE=‘0’ and DP_TI_LENGTH = N_(TI), while P_(I) = 1.

In each DP, the TI memory stores the input XFECBLOCKs (output XFECBLOCKsfrom the SSD/MIMO encoding block). Assume that input XFECBLOCKs aredefined as

(d_(n, s, 0, 0), d_(n, s, 0, 1), …  , d_(n, s, 0, N_(cells) − 1), d_(n, s, 1, 0), …  , d_(n, s, 1, N_(cells) − 1), …    , d_(n, s, N_(xBlock _ TI)(n, s) − 1, 0), …  , d_(n, s, N_(xBLOCK _ TI)(n, s) − 1, N_(cells) − 1)),

where d_(n,s,r,q) is the q^(th) cell of the r^(th) XFECBLOCK in thes^(th) TI block of the n^(th) TI group and represents the outputs of SSDand MIMO encodings as follows

$d_{n,s,r,q} = \left\{ {\begin{matrix}f_{n,s,r,q} & {,{{theoutputof}\mspace{14mu}{SSD}\mspace{14mu}\ldots\mspace{14mu}{encoding}}} \\q_{n,s,r,q} & {,{{theoutputof}\mspace{14mu}{MIMO}\mspace{14mu}{encoding}}}\end{matrix}\;.}\; \right.$

In addition, assume that output XFECBLOCKs from the time interleaver5050 are defined as

(h_(n, s, 0), h_(n, s, 1), …  , h_(n, s, i), …  , h_(n, s, N_(xBLOCK _ TI)(n, s) × N_(cells) − 1)),

where h_(n,s,i) is the i^(th) output cell (for i=0, . . . , N_(xBLOCK)_(_) _(TI)(n,s)×N_(cells)−1) in the s^(th) TI block of the n^(th) TIgroup.

Typically, the time interleaver will also act as a buffer for DP dataprior to the process of frame building. This is achieved by means of twomemory banks for each DP. The first TI-block is written to the firstbank. The second TI-block is written to the second bank while the firstbank is being read from and so on.

The TI is a twisted row-column block interleaver. For the s^(th) TIblock of the n^(th) TI group, the number of rows N_(r) of a TI memory isequal to the number of cells N_(cells), i.e., N_(r)=N_(cells) while thenumber of columns N_(c) is equal to the number N_(xBLOCK) _(_) _(TI)(n,s).

FIG. 26 illustrates the basic operation of a twisted row-column blockinterleaver according to an embodiment of the present invention.

(j) shows a writing operation in the time interleaver 5050 and (b) showsa reading operation in the time interleaver 5050. The first XFECBLOCK iswritten column-wise into the first column of the TI memory, and thesecond XFECBLOCK is written into the next column, and so on as shown in(a). Then, in the interleaving array, cells are read out diagonal-wise.During diagonal-wise reading from the first row (rightwards along therow beginning with the left-most column) to the last row, N_(r) cellsare read out as shown in (b). In detail, assuming z_(n,s,i)=0, . . . ,N_(r)N_(c)) as the TI memory cell position to be read sequentially, thereading process in such an interleaving array is performed bycalculating the row index R_(n,s,i), the column index c_(n,s,i), and theassociated twisting parameter T_(n,s,i) as follows expression.

$\begin{matrix}{{{{GENERATE}\left( {R_{n,s,i},C_{n,s,i}} \right)} = \left\{ {{R_{n,s,i} = {{mod}\left( {i,N_{r}} \right)}},{T_{n,s,i} = {{{{mod}\left( {{S_{shift} \times R_{n,s,i}},N_{c}} \right)}C_{n,s,i}} = {{mod}\left( {{T_{n,s,i} + \left\lfloor \frac{i}{N_{r}} \right\rfloor},N_{c}} \right)}}}} \right\}},} & \left\lbrack {{Expression}\mspace{14mu} 9} \right\rbrack\end{matrix}$

where s_(shift) is a common shift value for the diagonal-wise readingprocess regardless of N_(xBLOCK TI) (n,s) and it is determined byN_(xBLOCK TI MAX) given in the PLS2-STAT as follows expression.

$\begin{matrix}{{for}\left\{ {\begin{matrix}{{N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}}^{\prime} = {N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}} + 1}},{{{if}\mspace{14mu} N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}}{mod}\; 2} = 0}} \\{{N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}}^{\prime} = N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}}},{{{if}\mspace{14mu} N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}}{mod}\; 2} = 1}}\end{matrix},{S_{shift} = {\frac{N_{{xBLOCK}\;\_\;{TI}\;\_\;{MAX}}^{\prime} - 1}{2}.}}} \right.} & \left\lbrack {{Expression}\mspace{14mu} 10} \right\rbrack\end{matrix}$

As a result, the cell positions to be read are calculated by acoordinate as z_(n,s,i)=N_(r)C_(n,s,i)+R_(n,s,i).

FIG. 27 illustrates an operation of a twisted row-column blockinterleaver according to another embodiment of the present invention.

More specifically, FIG. 27 illustrates the interleaving array in the TImemory for each TI group, including virtual XFECBLOCKs when N_(xBLOCK)_(_) _(TI) (0,0)=3, N_(xBLOCK) _(_) _(TI) (1,0)=6, N_(xBLOCK) _(_) _(TI)(2,0)=5.

The variable number N_(xBLOCK) _(_) _(TI) (n,s)=N_(r) will be less thanor equal to N′_(xBLOCK) _(_) _(TI) _(_) _(MAX). Thus, in order toachieve a single-memory deinterleaving at the receiver side, regardlessof N_(xBLOCK) _(_) _(TI) (n,s), the interleaving array for use in atwisted row-column block interleaver is set to the size ofN_(r)×N_(c)=N_(cells)×N′_(xBLOCK) _(_) _(TI) _(_) _(MAX) by insertingthe virtual XFECBLOCKs into the TI memory and the reading process isaccomplished as follow expression.p=0;for i=0;i<N _(cells) N′ _(xBLOCK) _(_) _(TI) _(_) _(MAX) ;i=i+1{GENERATE(R _(n,s,i) ,C _(n,s,i));V _(i) =N _(r) C _(n,s,j) +R _(n,s,j)if V _(i) <N _(cells) N _(xBLOCK) _(_) _(TI)(n,s){Z _(n,s,p) =V _(i) ;p=p+1;}}  [Expression 11]

The number of TI groups is set to 3. The option of time interleaver issignaled in the PLS2-STAT data by DP_TI_TYPE=‘0’, DP_FRAME_INTERVAL=‘1’,and DP_TI_LENGTH=‘1’, i.e., N_(TI)=1, I_(JUMP)=1, and P₁=1. The numberof XFECBLOCKs, each of which has N_(cells)=30 cells, per TI group issignaled in the PLS2-DYN data by N_(xBLOCK) _(_) _(TI) (0,0)=3,N_(xBLOCK) _(_) _(TI) (1,0)=6, and N_(xBLOCK) _(_) _(TI) (2,0)=5,respectively. The maximum number of XFECBLOCK is signaled in thePLS2-STAT data by N_(xBLOCK) _(_) _(Group) _(_) _(MAX) which leads to└N_(xBLOCK) _(_) _(Group) _(_) _(MAX)/N_(TI)┘=N_(xBLOCK) _(_) _(TI) _(_)_(MAX)=6.

FIG. 28 illustrates a diagonal-wise reading pattern of a twistedrow-column block interleaver according to an embodiment of the presentinvention.

More specifically FIG. 28 shows a diagonal-wise reading pattern fromeach interleaving array with parameters of N′_(xBLOCK) _(_) _(TI) _(_)_(MAX)=7 and S_(shift)=(7−1)/2=3. Note that in the reading process shownas pseudocode above, if V_(i)≧N_(cells)N_(xBLOCK) _(_) _(TI) (n,s), thevalue of V_(i) is skipped and the next calculated value of V_(i) isused.

FIG. 29 illustrates interleaved XFECBLOCKs from each interleaving arrayaccording to an embodiment of the present invention.

FIG. 29 illustrates the interleaved XFECBLOCKs from each interleavingarray with parameters of N_(xBLOCK) _(_) _(TI) _(_) _(MAX)=7 andS_(shift)=3.

Hereinafter, a frequency interleaving procedure according to anembodiment of the present invention will be described.

The purpose of the frequency interleaver 7020 in the present invention,which operates on a single OFDM symbol, is to provide frequencydiversity by randomly interleaving data cells received from the cellmapper 7010. In order to get maximum interleaving gain in a singlesignal frame (or frame), a different interleaving-seed is used for everyOFDM symbol pair comprised of two sequential OFDM symbols.

The frequency interleaver 7020 may interleave cells in a transport blockas a unit of a signal frame to acquire additional diversity gain.According to an embodiment of the present invention, the frequencyinterleaver 7020 may apply different interleaving seeds to at least oneOFDM symbol or apply different interleaving seeds to a frame including aplurality of OFDM symbols.

In the present invention, the aforementioned frequency interleavingmethod may be referred to as random frequency interleaving (random FI).

In addition, according to an embodiment of the present invention, therandom FI may be applied to a super-frame structure including aplurality of signal frames with a plurality of OFDM symbols.

As described above, a broadcast signal transmitting apparatus or afrequency interleaver 7020 therein according to an embodiment of thepresent invention may apply different interleaving seeds (orinterleaving patterns) for at least one OFDM symbol, that is, for eachOFDM symbol or each of pair-wise OFDM symbols (or each OFDM symbol pair)and perform the random FI, thereby acquiring frequency diversity. Inaddition, the frequency interleaver 7020 according to an embodiment ofthe present invention may apply different interleaving seed for eachrespective signal frame and perform the random FI, thereby acquiringadditional frequency diversity.

Accordingly, a broadcast transmitting apparatus or a frequencyinterleaver 7020 according to an embodiment of the present invention mayhave a ping-pong frequency interleaver 7020 structure that performfrequency interleaving in units of one pair of consecutive OFDM symbols(pair-wise OFDM symbol) using two memory banks. Hereinafter, aninterleaving operation of the frequency interleaver 7020 according to anembodiment of the present invention may be referred to as pair-wisesymbol FI (or pair-wise FI) or ping-pong FI (ping-pong interleaving).The aforementioned interleaving operation corresponds to an embodimentof the random FI, which can be changed according to a designer'sintention.

Even-indexed pair-wise OFDM symbols and odd pair-wise OFDM symbols maybe intermittently (independently) interleaved via different FI memorybanks. In addition, the frequency interleaver 7020 according to anembodiment of the present invention may simultaneously perform readingand writing operations on one pair of consecutive OFDM symbols input toeach memory bank using an arbitrary interleaving seed. A detailedoperation will be described below.

In addition, according to an embodiment of the present invention, as alogical frequency interleaving operation for logically and effectivelyinterleaving all OFDM symbols in a super-frame, an interleaving seed isbasically changed in units of one pair of OFDM symbols.

Logical FI operation in order to reasonably and efficiently interleaveall OFDM symbols within a single frame, especially using differentinterleaving seeds. Basically, change interleaving seed every OFDMsymbol pair.

In addition, according to an embodiment of the present invention,various interleaving seeds may be generated by cyclic-shifting one maininterleaving seed in order to effectively change an interleaving seed.That is different interleaving seed to be used every OFDM symbol paircan be generated by cyclic-shifting one interleaving seed (maininterleaving seed). In this case, a cyclic-shifting rule may behierarchically defined in consideration of OFDM symbol and signal frameunits. Therefore, the symbol offset according to the present inventionmay be referred as a cyclic shifting value. This can be changedaccording to a designer's intention, which will be described in detail.

A broadcast signal receiving apparatus according to an embodiment of thepresent invention may perform an inverse procedure of the aforementionedrandom frequency interleaving. In this case, the broadcast signalreceiving apparatus or a frequency deinterleaver thereof according to anembodiment of the present invention may not use a ping-pong structureusing a double-memory and may perform deinterleaving on consecutiveinput OFDM symbols via a single-memory. Accordingly, memory useefficiency can be enhanced. In addition, reading and writing operationsare still required, which is called as a single-memory deinterleavingoperation. Such a deinterleaving scheme is very efficient in amemory-use aspect.

FIG. 30 is a view illustrating an operation of a frequency interleaver7020 according to an embodiment of the present invention.

FIG. 30 illustrates the basic operation of the frequency interleaver7020 using two memory banks at the transmitter, which enables asingle-memory deinterleaving at the receiver.

As described above, the frequency interleaver 7020 according to anembodiment of the present invention may perform a ping-pong interleavingoperation.

Typically, ping-pong interleaving operation is accomplished by means oftwo memory banks. In the proposed FI operation, two memory banks are foreach pair-wise OFDM symbol.

The maximum memory ROM (Read Only Memory) size for interleaving isapproximately two times to a maximum FFT size. At a transmit side, theROM size increase is rather less critical, compared to a receiver side.

As described above, odd pair-wise OFDM symbols and odd pair-wise OFDMsymbols may be intermittently interleaved via different FI memory-banks.That is, the second (odd-indexed) pair-wise OFDM symbol is interleavedin the second bank, while the first (even-indexed) pair-wise OFDM symbolis interleaved in the first bank and so on. For each pair-wise OFDMsymbol, a single interleaving seed is used. Based on the interleavingseed and reading-writing (or writing-reading) operation, two OFDMsymbols are sequentially interleaved.

Reading-writing operations according to an embodiment of the presentinvention are simultaneously accomplished without a collision.Writing-reading operations according to an embodiment of the presentinvention are simultaneously accomplished without a collision.

FIG. 30 illustrates an operation of the aforementioned frequencyinterleaver 7020. As illustrated in FIG. 30, the frequency interleaver7020 may include a demux 16000, two memory banks, a memory bank-A 16100and a memory bank-B 16200, and a demux 16300.

First, the frequency interleaver 7020 according to an embodiment of thepresent invention may perform a demultiplexing processing to the inputsequential OFDM symbols for the pair-wise OFDM symbol FI. Then thefrequency interleaver 7020 according to an embodiment of the presentinvention performs a reading-writing FI operation in each memory bank Aand B with a single interleaving seed. As shown in FIG. 30, two memorybanks are used for each OFDM symbol pair. Operationally, the first(even-indexed) OFDM symbol pair is interleaved in memory bank-A, whilethe second (odd-indexed) OFDM symbol pair is interleaved in memorybank-B and so on, alternating between A and B.

Then the frequency interleaver 7020 according to an embodiment of thepresent invention may perform a multiplexing processing to ping-pong FIoutputs for sequential OFDM symbol transmission.

FIG. 31 illustrates a basic switch model for MUX and DEMUX proceduresaccording to an embodiment of the present invention.

FIG. 31 illustrates simple operations the DEMUX and MUX applied inputand output of memory-bank-A/-B in the aforementioned ping-pong FIstructure.

The DEMUX and MUX may control the input sequential OFDM symbols to beinterleaved, and the output OFDM symbol pair to be transmitted,respectively. Different interleaving seeds are used for every OFDMsymbol pair.

Hereinafter, reading-writing operations of frequency interleavingaccording to an embodiment of the present invention will be described.

A frequency interleaver 7020 according to an embodiment of the presentinvention may select or use a single interleaving see and use theinterleaving seed in writing and reading operations for the first andsecond OFDM symbols, respectively. That is, the frequency interleaver7020 according to an embodiment of the present invention may use the oneselected arbitrary interleaving seed in an operation of writing a firstOFDM symbol of a pair-wise OFDM symbol, and use a second OFDM symbol ina reading operation, thereby achieving effective interleaving.Virtually, it seems like that two different interleaving seeds areapplied to two OFDM symbols, respectively.

Details of the reading-writing operation according to an embodiment ofthe present invention are as follows:

For the first OFDM symbol, the frequency interleaver 7020 according toan embodiment of the present invention may perform random writing intomemory (according to an interleaving seed) and perform then linearreading. For the second OFDM symbol, the frequency interleaver 7020according to an embodiment of the present invention may perform linearwriting into memory, (affected by the linear reading operation for thefirst OFDM symbol), simultaneously. Also, the frequency interleaver 7020according to an embodiment of the present invention may perform thenrandom reading (according to an interleaving seed).

As described above, the broadcast signal receiving apparatus accordingto an embodiment of the present invention may continuously transmit aplurality of frames on the time axis. In the present invention, a set ofsignal frames transmitted for a predetermined period of time may bereferred to as a super-frame. Accordingly, one super-frame may include Nsignal frames and each signal frame may include a plurality of OFDMsymbols.

FIG. 32 illustrates an operation of a memory bank according to anembodiment of the present invention.

As described above, two memory banks according to an embodiment of thepresent invention may apply an arbitrary interleaving seed generated viathe aforementioned procedure to each pair-wise OFDM symbol. In addition,each memory bank may change interleaving seed every pair-wise OFDMsymbol.

FIG. 33 illustrates a frequency deinterleaving procedure according to anembodiment of the present invention.

A broadcast signal receiving apparatus according to an embodiment of thepresent invention may perform an inverse procedure of the aforementionedfrequency interleaving procedure. FIG. 33 illustrates single-memorydeinterleaving (FDI) for input sequential OFDM symbols.

Basically, frequency deinterleaving operation follows to the inverseprocessing of frequency interleaving operation. For a single-memory use,no further processing is required.

When pair-wise OFDM symbols illustrated in a left portion of FIG. 33 areinput, the broadcast signal receiving apparatus according to anembodiment of the present invention may perform the aforementionedreading and writing operation using a single memory, as illustrated in aright portion of FIG. 33. In this case, the broadcast signal receivingapparatus according to an embodiment of the present invention maygenerate a memory-index and perform frequency deinterleaving (readingand writing) corresponding to an inverse procedure of frequencyinterleaving (writing and reading) performed by a broadcast signaltransmitting apparatus. The benefit is inherently caused by the proposedpair-wise ping-pong interleaving architecture.

The following mathematical formulae show the aforementionedreading-writing operation.for j=0,1, . . . , N _(sym) and k=0,1, . . . , N _(data)F _(j)(C _(j)(k))=X _(j)(k)where C _(j)(k) is a random seed generated by a random generator,in the ith pair-wise OFDM symbolF _(j) =[F _(j)(0),F _(j)(1), . . . ,F _(j)(N _(data)−2),F _(j)(N_(data)−1)], where N _(data) is the number of data cellsX _(j) =[X _(j)(0),X _(j)(1), . . . ,X _(j)(N _(data)−2),X _(j)(N_(data)−1)]  [Expression 12]for j=0,1, . . . , N _(sym) and k=0,1, . . . , N _(data)F _(j)(k)=X _(j)(C _(j)(k))where C _(j)(k) is the same random seed used for the first symbolF _(j) =[F _(j)(0),F _(j)(1), . . . ,F _(j)(N _(data)−2),F _(j)(N_(data)−1)], where N _(data) is the number of data cellsX _(j) =[X _(j)(0),X _(j)(1), . . . ,X _(j)(N _(data)−2),X _(j)(N_(data)−1)]  [Expression 13]

The above expression 12 is for the first OFDM symbol, i.e., (j mod 2)=0of the ith pair-wise OFDM symbol. The above expression 13 is for thesecond OFDM symbol, i.e., (j mod 2)=1 of the ith pair-wise OFDM symbol.Fj denotes an interleaved vector of the jth OFDM symbol (vector) and Xjdenotes an input vector of the jth OFDM symbol (vector). As shown in theexpressions, the reading-writing operation according to an embodiment ofthe present invention may be performed by applying one random seedgenerated by an arbitrary random generator to a pair-wise OFDM symbol.

FIG. 34 is a view illustrates concept of frequency interleaving appliedto a single signal frame according to an embodiment of the presentinvention.

As described above, a frequency interleaver 7020 according to anembodiment of the present invention may change interleaving seed everypair-wise OFDM symbol in a single frame. Details thereof will bedescribed below.

FIG. 35 is a view illustrating logical operation mechanism of frequencyinterleaving applied to a single signal frame according to an embodimentof the present invention.

FIG. 35 illustrates logical operation mechanism of a frequencyinterleaver 7020 and related parameter thereof, for effectively changinginterleaving seeds to be used the one single signal frame described withreference to FIG. 34.

As described above, in the present invention, various interleaving seedcan be effectively generated by cyclic-shifting one main interleavingseed by as much as an arbitrary symbol offset. As illustrated in FIG.35, according to an embodiment of the present invention, theaforementioned symbol offset may be differently generated for eachpair-wise OFDM symbol to generate different interleaving seeds. In thiscase, the symbol offset may be differently generated for each pair-wiseOFDM symbol using an arbitrary random symbol offset generator.

Hereinafter, the logical operation mechanism will be described.

As illustrated in a lower block of FIG. 35, a frequency interleaver 7020according to an embodiment of the present invention may randomlygenerate a symbol offset to be applied to each OFDM symbol included ineach signal frame using an input symbol index. The symbol offset (or arandom symbol offset) according to an embodiment of the presentinvention may be generated by an arbitrary random generator (or a symboloffset generator) included in a frequency interleaver 7020. In thiscase, when a frame index is reset, the symbol offset for each symbol isgenerated for symbols in each signal frame identified according to aframe index. In addition, the frequency interleaver 7020 according to anembodiment of the present invention may generate various interleavingseeds by cyclic-shifting a main interleaving seed for each OFDM symbolby as much as the generated symbol offset.

Then, as illustrated in an upper block of FIG. 35, a frequencyinterleaver 7020 according to an embodiment of the present invention mayperform random FI on cells included in each OFDM symbol using an inputcell index. A random FI parameter according to an embodiment of thepresent invention may be generated by a random FI generator included ina frequency interleaver 7020.

FIG. 36 illustrates expressions of logical operation mechanism offrequency interleaving applied to a single signal frame according to anembodiment of the present invention.

FIG. 36 illustrates a correlation of the aforementioned symbol offsetparameter and a parameter of random FI applied to a cell included ineach OFDM. As illustrated in FIG. 39, an offset to be used in each OFDMsymbol may be generated through a hierarchical structure of theaforementioned symbol offset generator. In this case, the symbol offsetgenerator may be designed using an arbitrary random generator.

The following expression shows a change procedure of interleaving seedin each of the aforementioned memory banks.for j=0,1, . . . , N _(sym) and for k=0,1, . . . , N _(data),F _(j)(C _(j)(k))=X _(j)(k)where C _(j)(k)=(T(k)+S _(└j/2┘))mod N _(data)T(k) is a main interleaving seed generated by a random generator, usedin the main FIS _(└j/2┘) is a random symbol offset generated by a random generator,used in the jth pair-wise OFDM symbol  [Expression 14]for j=0,1, . . . , N _(sym) and k=0,1, . . . , N _(data)F _(j)(k)=X _(j)(C _(j)(k))where C _(j)(k) is the same random seed used for the firstsymbol  [Expression 15]

The above expression 14 is for the first OFDM symbol, i.e., (j mod 2)=0of the ith pair-wise OFDM symbol and the above expression 15 is for thesecond OFDM symbol, i.e., (j mod 2)=1 of the ith pair-wise OFDM symbol.T(k) is a random sequence and correspond to a main random interleavingsequence or a single interleaving seed according to an embodiment of thepresent invention. The random sequence can be generated by the randominterleaving-sequence generator or a random main-sequence generatorwhich will be described later. S_(└j/2┘) is a symbol offset and can bereferred as a cyclic shifting value which is generated based on asub-PRBS sequence. The details will be described later.

FIG. 37 is a view illustrating single-memory deinterleaving for inputsequential OFDM symbols.

FIG. 37 is a view illustrating concept of a broadcast signal receivingapparatus or a frequency deinterleaver thereof, for applyinginterleaving seed used in a broadcast signal transmitting apparatus (ora frequency interleaver 7020) to each pair-wise OFDM symbol to performdeinterleaving.

As described above, the broadcast signal receiving apparatus accordingto an embodiment of the present invention may perform an inverseprocedure of the aforementioned frequency interleaving procedure using asingle memory. FIG. 37 illustrates an operation of the broadcast signalreceiving apparatus for processing single-memory deinterleaving (FDI)for input sequential OFDM symbols.

The broadcast signal receiving apparatus according to an embodiment ofthe present invention may perform an inverse procedure of theaforementioned operation of a frequency interleaver 7020. Thus,deinterleaving seeds correspond to the aforementioned interleaving seed.

The interleaving process for the OFDM symbol pair in each memorybank-A/B is described as above, exploiting a single interleaving-seed.The available data cells (the output cells from the cell mapper 7010) tobe interleaved in one OFDM symbol. The N_(data) according to theembodiment of the present invention is equal to the number of the datacells in one OFDM symbol. The maximum value of the N_(data) can bereferred as N_(max) and N_(max) is a parameter for frequencyinterleaving and may be differently defined according to each FFT mode.For the OFDM symbol pair in each memory bank, the interleaved OFDMsymbol pair is shown in FIG. 38.

Hj(k) is the interleaving address generated by randominterleaving-sequence generator for each FFT mode. The composition ofthe random interleaving-sequence generator will be described later. Asdescribed above, the purpose of the frequency interleaver 7020, whichoperates on a single OFDM symbol, is to provide frequency diversity byrandomly interleaving data cells. In order to get maximum interleavinggain in a single frame, a different interleaving-seed is used for everyOFDM symbol pair comprised of two sequential OFDM symbols. As shown inFIG. 38, the different interleaving seed can be generated based on theinterleaving address generated by a random interleaving-sequencegenerator.

Also, the different interleaving seed can be generated based on thecyclic shifting value as above mentioned. That means, differentinterleaving address to be used every symbol pair may be generated byusing the cyclic shifting value for every OFDM symbol pair.

As described above, an OFDM generation block 1030 may perform FFTtransformation on input data. Hereinafter, an operation of the frequencyinterleaver 7020 having the random interleaving-sequence generatoraccording to another embodiment will be described. As described above,an FFT size according to an embodiment of the present invention may be1K, 2K, 4K, 8K, 16K, 32K, 64K or the like, and it can be changedaccording to the designer's intention. Therefore an interleaving seed(or main interleaving seed) can be variable based on the FFT size.

FIG. 38 is a view illustrating an interleaving process according toaccording to an embodiment of the present invention.

The interleaving process for the OFDM symbol pair in each memorybank-A/B is described as above, exploiting the singleinterleaving-sequence. First, available data cells (the output cellsfrom the cell mapper 7010) to be interleaved in one OFDM symbol may bedefined as shown in FIG. 38. In the present invention, N_(data) is thenumber of data cells. N_(data)=C_(FSS) for the frame signalingsymbol(s), N_(data)=C_(data) for the normal data, and N_(data)=C_(FES)for the frame edge symbol. In addition, the interleaved data cells aredefined as shown in FIG. 38.

Therefore, the available data cells shown in FIG. 38 can be an input ofthe frequency interleaver 7020 according to an embodiment of the presentinvention and the interleaved data cells shown in FIG. 38 can be anoutput of the frequency interleaver 7020 according to an embodiment ofthe present invention.

FIG. 39 illustrates expressions of the interleaved OFDM symbol pairaccording to an embodiment of the present invention.

For the OFDM symbol pair in each memory bank, the interleaved OFDMsymbol pair may be represented as shown in FIG. 39. FIG. 39 is anotherembodiment of FIG. 38. The expression in FIG. 39 is different from theexpression in FIG. 38 and the basic functions of the two expressions aresimilar.

The block illustrated in an upper portion of FIG. 39 shows expressionsfor the first OFDM symbol of each pair, the block illustrated in a lowerportion of FIG. 39 shows expressions for the second OFDM symbol of eachpair. The word “a random generator” illustrated each portion of FIG. 39may be a random interleaving-sequence generator and the randominterleaving-sequence generator can be included in the frequencyinterleaver 7020.

HI(p) may be referred as Hj(k), which is the interleaving addressgenerated by random interleaving-sequence generator for each FFT mode.

Hereinafter, an operation of the random interleaving-sequence generatoraccording to an embodiment of the present invention will be described.The random interleaving-sequence generator may be included in thefrequency interleaver 7020 and be referred as a random seed generator.Also, the random interleaving-sequence generator according to anembodiment of the present invention can be referred as aninterleaving-address generator or a PRBS generator. It can be changedaccording to the designer's indention.

The random interleaving-sequence generator according an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol

a random symbol-offset generator (or a symbol-offset generator) forchanging a symbol offset (the cyclic shifting value). The randommain-sequence generator can be referred as a main-sequence generator.

Also, the random main-sequence generator may be referred as a main-PRBSgenerator and it may be changed according to the designer's attention.In the present invention, the output of the random main-sequencegenerator according to an embodiment of the present invention can bereferred as a main-PRBS sequence. It can be changed according to thedesigner's intention.

Also, the random symbol-offset generator according to an embodiment ofthe present invention may be referred as a sub-PRBS generator and theoutput of the random symbol-offset generator according to an embodimentof the present invention can be referred as a sub PRBS sequence. It canbe changed according to the designer's intention.

Hereinafter, the main-PRBS generator and sub-PRBS generator for use inall FFT modes are described.

FIG. 40 illustrates expressions representing an operation of themain-PRBS generator according to an embodiment of the present invention.

As shown in FIG. 40, the main-PRBS generator according to an embodimentof the present invention can be defined based on the bit binary wordsequence Rn and Rn can be defined according to the FFT mode (or FFTsize).

FIG. 41 illustrates expressions representing an operation of thesub-PRBS generator according to an embodiment of the present invention.

As shown in FIG. 41, the sub-PRBS generator according to an embodimentof the present invention can be defined bit binary word sequence Gk andGk can be defined based according to the FFT mode (or FFT size).

FIG. 42 illustrates expressions representing an operation of calculatingthe interleaving address and the cyclic shifting value according to anembodiment of the present invention.

As shown in the upper portion of FIG. 42, consequently, from theaforementioned main-PRBS generator and sub-PRBS generator, aninterleaving address to be used every OFDM symbol pair HI(p) can becalculated. Also, as shown in the lower portion of FIG. 42, the cyclicshifting value can be calculated for every OFDM symbol pair based on theoutput of the sub-PRBS generator.

FIG. 43 illustrates table representing parameters related to thefrequency interleaving according to an embodiment of the presentinvention.

FIG. 43 (a) shows a value of Nmax according to an embodiment of thepresent invention which can be defined according to the FFT mode (or theFFT size). FIG. 43 (b) shows a value of two-bit toggling which is usedto calculate the cyclic shifting value. Each value of the parameters canbe changed according to the designer's intention.

Hereinafter, the block diagrams of the interleaving-address generatorcomposed of the main-PRBS generator and the sub-PRBS generator for eachFFT mode are described.

FIG. 44 illustrates expressions illustrating an interleaving-addressgenerator for 8K FFT mode according to an embodiment of the presentinvention.

The interleaving-address generator for 8K FFT mode according to anembodiment of the present invention may include a main-PRBS generatorbased on 12 bits main-PRBS sequence 1 bit toggling, a sub-PRBS generatorbased on 11 bits sub-PRBS sequence 2 bits toggling, a modulo operatorand a memory index check.

As shown in FIG. 44, the modulo operator according to an embodiment ofthe present invention can be located before the memory-index check.

The locations of the modulo operator and the memory-index check is toincrease a frequency deinterleaving performance of the frequencydeinterleaver having single memory. As above described, a signal frame(or frame) according to the present invention may have normal datasymbol (normal data symbol), frame edge symbol and frame signalingsymbol and a length of the frame edge symbol and the frame signalingsymbol may be shorter than the normal data symbol. For this reason, afrequency deinterleaving performance of the frequency deinterleaverhaving single memory can be decreased. In order to increase thefrequency deinterleaving performance of the frequency deinterleaver witha single memory, the present invention may provide the operation of themodulo operator before the memory-index check.

The details are same as that given above in relation to FIGS. 40 to 43and thus description thereof is omitted.

FIG. 45 illustrates expressions illustrating an interleaving-addressgenerator for 16K FFT mode according to an embodiment of the presentinvention.

The interleaving-address generator for 16K FFT mode according to anembodiment of the present invention may include a main-PRBS generatorbased on 13 bits main-PRBS sequence 1 bit toggling, a sub-PRBS generatorbased on 12 bits sub-PRBS sequence 2 bits toggling, a modulo operatorand a memory index check. The details are same as that given above inrelation to FIGS. 40 to 44 and thus description thereof is omitted.

FIG. 46 illustrates expressions illustrating an interleaving-addressgenerator for 32K FFT mode according to an embodiment of the presentinvention.

The interleaving-address generator for 32K FFT mode according to anembodiment of the present invention may include a main-PRBS generatorbased on 14 bits main-PRBS sequence 1 bit toggling, a sub-PRBS generatorbased on 13 bits sub-PRBS sequence 2 bits toggling, a modulo operatorand a memory index check. The details are same as that given above inrelation to FIGS. 40 to 44 and thus description thereof is omitted.

Hereinafter, the random interleaving-sequence generator for a 1K FFTmode will be described.

The random interleaving-sequence generator according to an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol and a random symbol-offset generator for changing a symbol offsetevery OFDM symbol (This parameter can be referred as a cyclic shiftingvalue).

The random main-sequence generator according to an embodiment of thepresent invention may include a toggling and a PN generator and performrendering a full randomness in frequency-domain. According to anembodiment of the present invention, in the case of 1K FFT mode, therandom main-sequence generator may include a 1 bit toggling and a 9 bitsPN generator. The random main-sequence generator according to anembodiment of the present invention may be referred as the main-PRBSgenerator which is defined based on the 9-bit binary word sequence (orbinary sequence).

The random symbol-offset generator (or a symbol-offset generator)according to an embodiment of the present invention may change a symboloffset of each OFDM symbol. That is, the random symbol-offset generatormay generate the aforementioned symbol offset. The random symbol-offsetgenerator according to an embodiment of the present invention mayinclude k PN generator. K may be differently set for the respective FFTmodes. According to an embodiment of the present invention, in the caseof 1K FFT mode, 9 bits PN generator may be used. The randomsymbol-offset generator according to an embodiment of the presentinvention may be referred as a sub-PRBS generator which is defined basedon k bits binary word sequence (or binary sequence).

FIG. 47 is a view of a 1K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

The 1K FFT mode random interleaving-sequence generator according to anembodiment of the present invention may include a main-sequencegenerator, a random symbol-offset generator, a modulo operator, amemory-index check and a PRBS control module.

Hereinafter, an operation of each block will be described.

The main-sequence generator may include a toggling and PN generator andmay provide full randomness during interleaving.

The symbol-offset generator may generate a symbol-offset forcyclic-shifting main interleaving-sequence generated by themain-interleaving sequence generator for each OFDM symbol pair. For 1KFFT mode, the symbol-offset generator may include 9 bits PN generator. Adetailed operation is the same as those describe above and thus are notdescribed here.

The modulo operator may be operated when input value exceeds D_(max).D_(max) is used to the interleaving according to an embodiment of thepresent invention and a value of D_(max) may be a half of the value ofthe N_(data)(N_(max)) which is above mentioned. D_(max) for 1K FFT modemay be 502.

The memory-index check and PRBS control module may not use output fromthe modulo operator when a memory-address is greater than D_(max) andmay repeatedly operate the main-sequence generator to adjust the outputmemory-address such that the output memory-index does not exceedD_(max).

Locations of the illustrated memory-index check and modulo operator canbe changed according to a designer's intention.

FIG. 48 illustrates expressions representing an operation of a 1K FFTmode main-sequence generator and symbol-offset generator according to anembodiment of the present invention.

FIG. 48 (a) shows expressions representing the operation of themain-sequence generator for 1K FFT mode and FIG. 48 (b) showsexpressions representing the operation of the symbol-offset generatorfor 1K FFT mode.

The expressions illustrated in an upper portion of FIG. 48 (a) showinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 9^(th)primitive polynomial and the initial value may be changed by arbitraryvalues. That is, the expressions illustrated in an upper portion showsbinary word sequences or binary bits used to define the main-PRBSgenerator which can generate main-PRBS sequence.

The expressions illustrated in a lower portion of FIG. 48 (a) showprocedures of calculating and outputting the interleaving address forthe interleaving sequence for an output signal of the toggling and thePN generator. As illustrated in the expression, one random symbol-offset(or a symbol offset or cyclic shifting value) is used to calculate theinterleaving sequence and the cyclic shifting value may be applied toeach OFDM symbol pair in the same way.

The parameter q_I may be an order of 0 and 1 which is applied to eachOFDM symbol and be used to an operation of toggling. Consequently, theoperation of toggling for each OFDM symbol can be represented as0,1,0,1, . . . or 1,0,1,0 . . . . In this case, the order of 0 and 1 ofthe parameter q_I can be randomly outputted.

The expressions illustrated in an upper portion of FIG. 48 (b) showsinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 9^(th)primitive polynomial and the initial value may be changed by arbitraryvalues.

The expressions illustrated in a lower portion of FIG. 48 (b) shows aprocedure for calculating and outputting a symbol-offset for outputsignals the toggling and the PN generator. As illustrated in theexpression, the symbol offset (cyclic shifting value) can be calculatedbased on the sub PRBS sequence and the random symbol-offset generatormay be operated for each OFDM symbol pair. Accordingly, the length of anentire output offset may correspond to half of the length of an entireOFDM symbol.

Hereinafter, a random interleaving-sequence generator for 1K FFT modeaccording to another embodiment of the present invention will bedescribed.

The random interleaving-sequence generator for 1K FFT mode according toanother embodiment of the present invention includes a main-sequencegenerator including bit shuffling.

FIG. 49 is a view illustrating a 1K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

The 1K FFT mode random interleaving-sequence generator according toanother embodiment of the present invention may include a main-sequencegenerator, a symbol-offset generator, a modulo operator, a memory-indexcheck and a PRBS control module.

Details thereof except bit shuffling have been described above and thuswill be omitted here.

The bit shuffling optimizes spreading properties or random propertiesand is designed in consideration of N_(data). In the case of 1K FFTmode, the bit shuffling may use a 9-bit PN generator, which can bechanged.

FIG. 50 is expressions representing operations of 1K FFT mode bitshuffling and 1K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

(a) illustrates an expression representing an operation of the 1K FFTmode bit shuffling and (b) illustrates an expression representing anoperation of the 1K FFT random interleaving-sequence generator.

The upper portion of (a) shows an operation of the 1K FFT mode bitshuffling and the lower portion of (a) shows an embodiment of the 1K FFTmode bit shuffling for 9 bits.

As illustrated in (a), the 1K FFT mode bit shuffling may mix bits ofregisters of a PN generator during calculation of a memory-index.

An expression illustrated in an upper portion of (b) shows initial valuesetting and primitive polynomial of a main-sequence generator. In thiscase, the primitive polynomial may be 9^(th) primitive polynomial andthe initial value may be changed by arbitrary values. That is, theexpressions illustrated in an upper portion shows binary word sequencesor binary bits used to define the main-PRBS generator which can generatemain-PRBS sequence.

An expression illustrated in a lower portion of (b) shows a procedure ofcalculating and outputting the interleaving address for an interleavingsequence for an output signal of the toggling and the PN generator. Asillustrated in the expression, one random symbol-offset (or a symboloffset or cyclic shifting value) is used to calculate the interleavingsequence and the cyclic shifting value may be applied to each OFDMsymbol pair in the same way.

Hereinafter, the random interleaving-sequence generator for a 2K FFTmode will be described.

The random interleaving-sequence generator according to an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol and a random symbol-offset generator for changing a symbol offsetevery OFDM symbol (This parameter can be referred as a cyclic shiftingvalue).

The random main-sequence generator according to an embodiment of thepresent invention may include a toggling and a PN generator and performrendering a full randomness in frequency-domain. According to anembodiment of the present invention, in the case of 2K FFT mode, therandom main-sequence generator may include a 1 bit toggling and a 10bits PN generator. The random main-sequence generator according to anembodiment of the present invention may be referred as the main-PRBSgenerator which is defined based on the 10-bit binary word sequence (orbinary sequence).

The random symbol-offset generator (or a symbol-offset generator)according to an embodiment of the present invention may change a symboloffset of each OFDM symbol. That is, the random symbol-offset generatormay generate the aforementioned symbol offset. The random symbol-offsetgenerator according to an embodiment of the present invention mayinclude k PN generator. K may be differently set for the respective FFTmodes. According to an embodiment of the present invention, in the caseof 2K FFT mode, 10 bits PN generator may be used. The randomsymbol-offset generator according to an embodiment of the presentinvention may be referred as a sub-PRBS generator which is defined basedon k bits binary word sequence (or binary sequence).

FIG. 51 is a view of a 2K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

The 2K FFT mode random interleaving-sequence generator according to anembodiment of the present invention may include a main-sequencegenerator, a random symbol-offset generator, a modulo operator, amemory-index check and a PRBS control module.

Hereinafter, an operation of each block will be described.

The main-sequence generator may include a toggling and PN generator andmay provide full randomness during interleaving.

The symbol-offset generator may generate a symbol-offset forcyclic-shifting main interleaving-sequence generated by themain-interleaving sequence generator for each OFDM symbol pair. For 2KFFT mode, the symbol-offset generator may include 10 bits PN generator.A detailed operation is the same as those describe above and thus arenot described here.

The modulo operator may be operated when input value exceeds D_(max).D_(max) is used to the interleaving according to an embodiment of thepresent invention and a value of D_(max) may be a half of the value ofthe N_(data)(N_(max)) which is above mentioned. D_(max) for 2K FFT modemay be 1024.

The memory-index check and PRBS control module may not use output fromthe modulo operator when a memory-address is greater than D_(max) andmay repeatedly operate the main-sequence generator to adjust the outputmemory-address such that the output memory-index does not exceedD_(max).

Locations of the illustrated memory-index check and modulo operator canbe changed according to a designer's intention.

FIG. 52 illustrates expressions representing an operation of a 2K FFTmode main-sequence generator and symbol-offset generator according to anembodiment of the present invention.

FIG. 52 (a) shows expressions representing the operation of themain-sequence generator for 2K FFT mode and FIG. 52 (b) showsexpressions representing the operation of the symbol-offset generatorfor 2K FFT mode.

The expressions illustrated in an upper portion of FIG. 52 (a) showinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 10^(th)primitive polynomial and the initial value may be changed by arbitraryvalues. That is, the expressions illustrated in an upper portion showsbinary word sequences or binary bits used to define the main-PRBSgenerator which can generate main-PRBS sequence.

The expressions illustrated in a lower portion of FIG. 52 (a) showprocedures of calculating and outputting the interleaving address forthe interleaving sequence for an output signal of the toggling and thePN generator. As illustrated in the expression, one random symbol-offset(or a symbol offset or cyclic shifting value) is used to calculate theinterleaving sequence and the cyclic shifting value may be applied toeach OFDM symbol pair in the same way.

The parameter q_I may be an order of 0 and 1 which is applied to eachOFDM symbol and be used to an operation of toggling. Consequently, theoperation of toggling for each OFDM symbol can be represented as0,1,0,1, . . . or 1,0,1,0 . . . . In this case, the order of 0 and 1 ofthe parameter q_I can be randomly outputted.

The expressions illustrated in an upper portion of FIG. 52 (b) showsinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 10^(th)primitive polynomial and the initial value may be changed by arbitraryvalues.

The expressions illustrated in a lower portion of FIG. 52 (b) shows aprocedure for calculating and outputting a symbol-offset for outputsignals of a toggling and a PN generator. As illustrated in theexpression, the symbol offset (cyclic shifting value) can be calculatedbased on the sub PRBS sequence and the random symbol-offset generatormay be operated for each OFDM symbol pair. Accordingly, the length of anentire output offset may correspond to half of the length of an entireOFDM symbol.

Hereinafter, a random interleaving-sequence generator for 2K FFT modeaccording to another embodiment of the present invention will bedescribed.

The random interleaving-sequence generator for 2K FFT mode according toanother embodiment of the present invention includes a main-sequencegenerator including bit shuffling.

FIG. 53 is a view illustrating a 2K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

The 2K FFT mode random interleaving-sequence generator according toanother embodiment of the present invention may include a main-sequencegenerator, a symbol-offset generator, a modulo operator, a memory-indexcheck and a PRBS control module.

Details thereof except bit shuffling have been described above and thuswill be omitted here.

The bit shuffling optimizes spreading properties or random propertiesand is designed in consideration of N_(data). In the case of 2K FFTmode, the bit shuffling may use a 10-bit PN generator, which can bechanged.

FIG. 54 is expressions representing operations of 2K FFT mode bitshuffling and 2K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

(a) illustrates an expression representing an operation of the 2K FFTmode bit shuffling and (b) illustrates an expression representing anoperation of the 2K FFT random interleaving-sequence generator.

The upper portion of (a) shows an operation of the 2K FFT mode bitshuffling and the lower portion of (a) shows an embodiment of the 2K FFTmode bit shuffling for 10 bits.

As illustrated in (a), the 2K FFT mode bit shuffling may mix bits ofregisters of a PN generator during calculation of a memory-index.

An expression illustrated in an upper portion of (b) shows initial valuesetting and primitive polynomial of a main-sequence generator. In thiscase, the primitive polynomial may be 9^(th) primitive polynomial andthe initial value may be changed by arbitrary values. That is, theexpressions illustrated in an upper portion shows binary word sequencesor binary bits used to define the main-PRBS generator which can generatemain-PRBS sequence.

An expression illustrated in a lower portion of (b) shows a procedure ofcalculating and outputting the interleaving address for an interleavingsequence for an output signal of the toggling and the PN generator. Asillustrated in the expression, one random symbol-offset (or a symboloffset or cyclic shifting value) is used to calculate the interleavingsequence and the cyclic shifting value may be applied to each OFDMsymbol pair in the same way.

Hereinafter, the random interleaving-sequence generator for a 4K FFTmode will be described.

The random interleaving-sequence generator according to an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol and a random symbol-offset generator for changing a symbol offsetevery OFDM symbol (This parameter can be referred as a cyclic shiftingvalue).

The random main-sequence generator according to an embodiment of thepresent invention may include a toggling and a PN generator and performrendering a full randomness in frequency-domain. According to anembodiment of the present invention, in the case of 4K FFT mode, therandom main-sequence generator may include a 1 bit toggling and an 11bits PN generator. The random main-sequence generator according to anembodiment of the present invention may be referred as the main-PRBSgenerator which is defined based on the 11-bit binary word sequence (orbinary sequence).

The random symbol-offset generator (or a symbol-offset generator)according to an embodiment of the present invention may change a symboloffset of each OFDM symbol. That is, the random symbol-offset generatormay generate the aforementioned symbol offset. The random symbol-offsetgenerator according to an embodiment of the present invention mayinclude k PN generator. K may be differently set for the respective FFTmodes. According to an embodiment of the present invention, in the caseof 4K FFT mode, 11 bits PN generator may be used. The randomsymbol-offset generator according to an embodiment of the presentinvention may be referred as a sub-PRBS generator which is defined basedon k bits binary word sequence (or binary sequence).

FIG. 55 is a view of a 4K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

The 4K FFT mode random interleaving-sequence generator according to anembodiment of the present invention may include a main-sequencegenerator, a random symbol-offset generator, a modulo operator, amemory-index check and a PRBS control module.

Hereinafter, an operation of each block will be described.

The main-sequence generator may include a toggling and PN generator andmay provide full randomness during interleaving.

The symbol-offset generator may generate a symbol-offset forcyclic-shifting main interleaving-sequence generated by themain-interleaving sequence generator for each OFDM symbol pair. For 4KFFT mode, the symbol-offset generator may include 11 bits PN generator.A detailed operation is the same as those describe above and thus arenot described here.

The modulo operator may be operated when input value exceeds D_(max).D_(max) is used to the interleaving according to an embodiment of thepresent invention and a value of D_(max) may be a half of the value ofthe N_(data)(N_(max)) which is above mentioned. D_(max) for 4K FFT modemay be 2048.

The memory-index check and PRBS control module may not use output fromthe modulo operator when a memory-address is greater than D_(max) andmay repeatedly operate the main-sequence generator to adjust the outputmemory-address such that the output memory-index does not exceedD_(max).

Locations of the illustrated memory-index check and modulo operator canbe changed according to a designer's intention.

FIG. 56 illustrates expressions representing an operation of a 4K FFTmode main-sequence generator and symbol-offset generator according to anembodiment of the present invention.

FIG. 56 (a) shows expressions representing the operation of themain-sequence generator for 4K FFT mode and FIG. 56 (b) showsexpressions representing the operation of the symbol-offset generatorfor 4K FFT mode.

The expressions illustrated in an upper portion of FIG. 56 (a) showinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 11^(th)primitive polynomial and the initial value may be changed by arbitraryvalues. That is, the expressions illustrated in an upper portion showsbinary word sequences or binary bits used to define the main-PRBSgenerator which can generate main-PRBS sequence.

The expressions illustrated in a lower portion of FIG. 56 (a) showprocedures of calculating and outputting the interleaving address forthe interleaving sequence for an output signal of the toggling and thePN generator. As illustrated in the expression, one random symbol-offset(or a symbol offset or cyclic shifting value) is used to calculate theinterleaving sequence and the cyclic shifting value may be applied toeach OFDM symbol pair in the same way.

The parameter q_I may be an order of 0 and 1 which is applied to eachOFDM symbol and be used to an operation of toggling. Consequently, theoperation of toggling for each OFDM symbol can be represented as0,1,0,1, . . . or 1,0,1,0 . . . . In this case, the order of 0 and 1 ofthe parameter q_I can be randomly outputted.

The expressions illustrated in an upper portion of FIG. 56 (b) showsinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 11^(th)primitive polynomial and the initial value may be changed by arbitraryvalues.

The expressions illustrated in a lower portion of FIG. 56 (b) shows aprocedure for calculating and outputting a symbol-offset for outputsignals of a toggling and a PN generator. As illustrated in theexpression, the symbol offset (cyclic shifting value) can be calculatedbased on the sub PRBS sequence and the random symbol-offset generatormay be operated for each OFDM symbol pair. Accordingly, the length of anentire output offset may correspond to half of the length of an entireOFDM symbol.

Hereinafter, a random interleaving-sequence generator for 4K FFT modeaccording to another embodiment of the present invention will bedescribed.

The random interleaving-sequence generator for 4K FFT mode according toanother embodiment of the present invention includes a main-sequencegenerator including bit shuffling.

FIG. 57 is a view illustrating a 4K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

The 4K FFT mode random interleaving-sequence generator according toanother embodiment of the present invention may include a main-sequencegenerator, a symbol-offset generator, a modulo operator, a memory-indexcheck and a PRBS control module.

Details thereof except bit shuffling have been described above and thuswill be omitted here.

The bit shuffling optimizes spreading properties or random propertiesand is designed in consideration of N_(data). In the case of 4K FFTmode, the bit shuffling may use an 11-bit PN generator, which can bechanged.

FIG. 58 is expressions representing operations of 4K FFT mode bitshuffling and 4K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

(a) illustrates an expression representing an operation of the 4K FFTmode bit shuffling and (b) illustrates an expression representing anoperation of the 4K FFT random interleaving-sequence generator.

The upper portion of (a) shows an operation of the 4K FFT mode bitshuffling and the lower portion of (a) shows an embodiment of the 4K FFTmode bit shuffling for 11 bits.

As illustrated in (a), the 4K FFT mode bit shuffling may mix bits ofregisters of a PN generator during calculation of a memory-index.

An expression illustrated in an upper portion of (b) shows initial valuesetting and primitive polynomial of a main-sequence generator. In thiscase, the primitive polynomial may be 9^(th) primitive polynomial andthe initial value may be changed by arbitrary values. That is, theexpressions illustrated in an upper portion shows binary word sequencesor binary bits used to define the main-PRBS generator which can generatemain-PRBS sequence.

An expression illustrated in a lower portion of (b) shows a procedure ofcalculating and outputting the interleaving address for an interleavingsequence for an output signal of the toggling and the PN generator. Asillustrated in the expression, one random symbol-offset (or a symboloffset or cyclic shifting value) is used to calculate the interleavingsequence and the cyclic shifting value may be applied to each OFDMsymbol pair in the same way.

Hereinafter, the random interleaving-sequence generator for an 8K FFTmode will be described.

The random interleaving-sequence generator according to an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol and a random symbol-offset generator for changing a symbol offsetevery OFDM symbol (This parameter can be referred as a cyclic shiftingvalue).

The random main-sequence generator according to an embodiment of thepresent invention may include a toggling and a PN generator and performrendering a full randomness in frequency-domain. According to anembodiment of the present invention, in the case of 8K FFT mode, therandom main-sequence generator may include a 1 bit toggling and a 12bits PN generator. The random main-sequence generator according to anembodiment of the present invention may be referred as the main-PRBSgenerator which is defined based on the 12-bit binary word sequence (orbinary sequence).

The random symbol-offset generator (or a symbol-offset generator)according to an embodiment of the present invention may change a symboloffset of each OFDM symbol. That is, the random symbol-offset generatormay generate the aforementioned symbol offset. The random symbol-offsetgenerator according to an embodiment of the present invention mayinclude k PN generator. K may be differently set for the respective FFTmodes. According to an embodiment of the present invention, in the caseof 8K FFT mode, 12 bits PN generator may be used. The randomsymbol-offset generator according to an embodiment of the presentinvention may be referred as a sub-PRBS generator which is defined basedon k bits binary word sequence (or binary sequence).

FIG. 59 is a view of an 8K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

The 8K FFT mode random interleaving-sequence generator according to anembodiment of the present invention may include a main-sequencegenerator, a random symbol-offset generator, a modulo operator, amemory-index check and a PRBS control module.

Hereinafter, an operation of each block will be described.

The main-sequence generator may include a toggling and PN generator andmay provide full randomness during interleaving.

The symbol-offset generator may generate a symbol-offset forcyclic-shifting main interleaving-sequence generated by themain-interleaving sequence generator for each OFDM symbol pair. For 8KFFT mode, the symbol-offset generator may include 12 bits PN generator.A detailed operation is the same as those describe above and thus arenot described here.

The modulo operator may be operated when input value exceeds D_(max).D_(max) is used to the interleaving according to an embodiment of thepresent invention and a value of D_(max) may be a half of the value ofthe N_(data)(N_(max)) which is above mentioned. D_(max) for 8K FFT modemay be 4096.

The memory-index check and PRBS control module may not use output fromthe modulo operator when a memory-address is greater than D_(max) andmay repeatedly operate the main-sequence generator to adjust the outputmemory-address such that the output memory-index does not exceedD_(max).

Locations of the illustrated memory-index check and modulo operator canbe changed according to a designer's intention.

FIG. 60 illustrates expressions representing an operation of an 8K FFTmode main-sequence generator and symbol-offset generator according to anembodiment of the present invention.

FIG. 60 (a) shows expressions representing the operation of themain-sequence generator for 8K FFT mode and FIG. 60 (b) showsexpressions representing the operation of the symbol-offset generatorfor 8K FFT mode.

The expressions illustrated in an upper portion of FIG. 60 (a) showinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 12^(th)primitive polynomial and the initial value may be changed by arbitraryvalues. That is, the expressions illustrated in an upper portion showsbinary word sequences or binary bits used to define the main-PRBSgenerator which can generate main-PRBS sequence.

The expressions illustrated in a lower portion of FIG. 60 (a) showprocedures of calculating and outputting the interleaving address forthe interleaving sequence for an output signal of the toggling and thePN generator. As illustrated in the expression, one random symbol-offset(or a symbol offset or cyclic shifting value) is used to calculate theinterleaving sequence and the cyclic shifting value may be applied toeach OFDM symbol pair in the same way.

The parameter q_I may be an order of 0 and 1 which is applied to eachOFDM symbol and be used to an operation of toggling. Consequently, theoperation of toggling for each OFDM symbol can be represented as0,1,0,1, . . . or 1,0,1,0 . . . . In this case, the order of 0 and 1 ofthe parameter q_I can be randomly outputted.

The expressions illustrated in an upper portion of FIG. 60 (b) showsinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 12^(th)primitive polynomial and the initial value may be changed by arbitraryvalues.

The expressions illustrated in a lower portion of FIG. 60 (b) shows aprocedure for calculating and outputting a symbol-offset for outputsignals of a toggling and a PN generator. As illustrated in theexpression, the symbol offset (cyclic shifting value) can be calculatedbased on the sub PRBS sequence and the random symbol-offset generatormay be operated for each OFDM symbol pair. Accordingly, the length of anentire output offset may correspond to half of the length of an entireOFDM symbol.

Hereinafter, a random interleaving-sequence generator for 8K FFT modeaccording to another embodiment of the present invention will bedescribed.

The random interleaving-sequence generator for 8K FFT mode according toanother embodiment of the present invention includes a main-sequencegenerator including bit shuffling.

FIG. 61 is a view illustrating an 8K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

The 8K FFT mode random interleaving-sequence generator according toanother embodiment of the present invention may include a main-sequencegenerator, a symbol-offset generator, a modulo operator, a memory-indexcheck and a PRBS control module.

Details thereof except bit shuffling have been described above and thuswill be omitted here.

The bit shuffling optimizes spreading properties or random propertiesand is designed in consideration of N_(data). In the case of 8K FFTmode, the bit shuffling may use a 12-bit PN generator, which can bechanged.

FIG. 62 is expressions representing operations of 8K FFT mode bitshuffling and 8K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

(a) illustrates an expression representing an operation of the 8K FFTmode bit shuffling and (b) illustrates an expression representing anoperation of the 8K FFT random interleaving-sequence generator.

The upper portion of (a) shows an operation of the 8K FFT mode bitshuffling and the lower portion of (a) shows an embodiment of the 8K FFTmode bit shuffling for 12 bits.

As illustrated in (a), the 8K FFT mode bit shuffling may mix bits ofregisters of a PN generator during calculation of a memory-index.

An expression illustrated in an upper portion of (b) shows initial valuesetting and primitive polynomial of a main-sequence generator. In thiscase, the primitive polynomial may be 9^(th) primitive polynomial andthe initial value may be changed by arbitrary values. That is, theexpressions illustrated in an upper portion shows binary word sequencesor binary bits used to define the main-PRBS generator which can generatemain-PRBS sequence.

An expression illustrated in a lower portion of (b) shows a procedure ofcalculating and outputting the interleaving address for an interleavingsequence for an output signal of the toggling and the PN generator. Asillustrated in the expression, one random symbol-offset (or a symboloffset or cyclic shifting value) is used to calculate the interleavingsequence and the cyclic shifting value may be applied to each OFDMsymbol pair in the same way.

Hereinafter, the random interleaving-sequence generator for a 16K FFTmode will be described.

The random interleaving-sequence generator according to an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol and a random symbol-offset generator for changing a symbol offsetevery OFDM symbol (This parameter can be referred as a cyclic shiftingvalue).

The random main-sequence generator according to an embodiment of thepresent invention may include a toggling and a PN generator and performrendering a full randomness in frequency-domain. According to anembodiment of the present invention, in the case of 16K FFT mode, therandom main-sequence generator may include a 1 bit toggling and a 13bits PN generator. The random main-sequence generator according to anembodiment of the present invention may be referred as the main-PRBSgenerator which is defined based on the 13-bit binary word sequence (orbinary sequence).

The random symbol-offset generator (or a symbol-offset generator)according to an embodiment of the present invention may change a symboloffset of each OFDM symbol. That is, the random symbol-offset generatormay generate the aforementioned symbol offset. The random symbol-offsetgenerator according to an embodiment of the present invention mayinclude k PN generator. K may be differently set for the respective FFTmodes. According to an embodiment of the present invention, in the caseof 16K FFT mode, 13 bits PN generator may be used. The randomsymbol-offset generator according to an embodiment of the presentinvention may be referred as a sub-PRBS generator which is defined basedon k bits binary word sequence (or binary sequence).

FIG. 63 is a view of a 16K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

The 16K FFT mode random interleaving-sequence generator according to anembodiment of the present invention may include a main-sequencegenerator, a random symbol-offset generator, a modulo operator, amemory-index check and a PRBS control module.

Hereinafter, an operation of each block will be described.

The main-sequence generator may include a toggling and PN generator andmay provide full randomness during interleaving.

The symbol-offset generator may generate a symbol-offset forcyclic-shifting main interleaving-sequence generated by themain-interleaving sequence generator for each OFDM symbol pair. For 16KFFT mode, the symbol-offset generator may include 13 bits PN generator.A detailed operation is the same as those describe above and thus arenot described here.

The modulo operator may be operated when input value exceeds D_(max).D_(max) is used to the interleaving according to an embodiment of thepresent invention and a value of D_(max) may be a half of the value ofthe N_(data)(N_(max)) which is above mentioned. D_(max) for 16K FFT modemay be 8192.

The memory-index check and PRBS control module may not use output fromthe modulo operator when a memory-address is greater than D_(max) andmay repeatedly operate the main-sequence generator to adjust the outputmemory-address such that the output memory-index does not exceedD_(max).

Locations of the illustrated memory-index check and modulo operator canbe changed according to a designer's intention.

FIG. 64 illustrates expressions representing an operation of a 16K FFTmode main-sequence generator and symbol-offset generator according to anembodiment of the present invention.

FIG. 64 (a) shows expressions representing the operation of themain-sequence generator for 16K FFT mode and FIG. 64 (b) showsexpressions representing the operation of the symbol-offset generatorfor 16K FFT mode.

The expressions illustrated in an upper portion of FIG. 64 (a) showinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 13^(th)primitive polynomial and the initial value may be changed by arbitraryvalues. That is, the expressions illustrated in an upper portion showsbinary word sequences or binary bits used to define the main-PRBSgenerator which can generate main-PRBS sequence.

The expressions illustrated in a lower portion of FIG. 64 (a) showprocedures of calculating and outputting the interleaving address forthe interleaving sequence for an output signal of the toggling and thePN generator. As illustrated in the expression, one random symbol-offset(or a symbol offset or cyclic shifting value) is used to calculate theinterleaving sequence and the cyclic shifting value may be applied toeach OFDM symbol pair in the same way.

The parameter q_I may be an order of 0 and 1 which is applied to eachOFDM symbol and be used to an operation of toggling. Consequently, theoperation of toggling for each OFDM symbol can be represented as0,1,0,1, . . . or 1,0,1,0 . . . . In this case, the order of 0 and 1 ofthe parameter q_I can be randomly outputted.

The expressions illustrated in an upper portion of FIG. 64 (b) showsinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 13^(th)primitive polynomial and the initial value may be changed by arbitraryvalues.

The expressions illustrated in a lower portion of FIG. 64 (b) shows aprocedure for calculating and outputting a symbol-offset for outputsignals of a toggling and a PN generator. As illustrated in theexpression, the symbol offset (cyclic shifting value) can be calculatedbased on the sub PRBS sequence and the random symbol-offset generatormay be operated for each OFDM symbol pair. Accordingly, the length of anentire output offset may correspond to half of the length of an entireOFDM symbol.

Hereinafter, a random interleaving-sequence generator for 16K FFT modeaccording to another embodiment of the present invention will bedescribed.

The random interleaving-sequence generator for 16K FFT mode according toanother embodiment of the present invention includes a main-sequencegenerator including bit shuffling.

FIG. 65 is a view illustrating a 16K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

The 16K FFT mode random interleaving-sequence generator according toanother embodiment of the present invention may include a main-sequencegenerator, a symbol-offset generator, a modulo operator, a memory-indexcheck and a PRBS control module.

Details thereof except bit shuffling have been described above and thuswill be omitted here.

The bit shuffling optimizes spreading properties or random propertiesand is designed in consideration of N_(data). In the case of 16K FFTmode, the bit shuffling may use a 13-bit PN generator, which can bechanged.

FIG. 66 is expressions representing operations of 16K FFT mode bitshuffling and 16K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

(a) illustrates an expression representing an operation of the 16K FFTmode bit shuffling and (b) illustrates an expression representing anoperation of the 16K FFT random interleaving-sequence generator.

The upper portion of (a) shows an operation of the 16K FFT mode bitshuffling and the lower portion of (a) shows an embodiment of the 16KFFT mode bit shuffling for 13 bits.

As illustrated in (a), the 16K FFT mode bit shuffling may mix bits ofregisters of a PN generator during calculation of a memory-index.

An expression illustrated in an upper portion of (b) shows initial valuesetting and primitive polynomial of a main-sequence generator. In thiscase, the primitive polynomial may be 9^(th) primitive polynomial andthe initial value may be changed by arbitrary values. That is, theexpressions illustrated in an upper portion shows binary word sequencesor binary bits used to define the main-PRBS generator which can generatemain-PRBS sequence.

An expression illustrated in a lower portion of (b) shows a procedure ofcalculating and outputting the interleaving address for an interleavingsequence for an output signal of the toggling and the PN generator. Asillustrated in the expression, one random symbol-offset (or a symboloffset or cyclic shifting value) is used to calculate the interleavingsequence and the cyclic shifting value may be applied to each OFDMsymbol pair in the same way.

Hereinafter, the random interleaving-sequence generator for a 32K FFTmode will be described.

The random interleaving-sequence generator according to an embodiment ofthe present invention may apply different interleaving seeds torespective OFDM symbols to acquire frequency diversity. Logicalcomposition of the random interleaving-sequence generator may include arandom main-sequence generator for interleaving cells in a single OFDMsymbol and a random symbol-offset generator for changing a symbol offsetevery OFDM symbol (This parameter can be referred as a cyclic shiftingvalue).

The random main-sequence generator according to an embodiment of thepresent invention may include a toggling and a PN generator and performrendering a full randomness in frequency-domain. According to anembodiment of the present invention, in the case of 32K FFT mode, therandom main-sequence generator may include a 1 bit toggling and a 14bits PN generator. The random main-sequence generator according to anembodiment of the present invention may be referred as the main-PRBSgenerator which is defined based on the 14-bit binary word sequence (orbinary sequence).

The random symbol-offset generator (or a symbol-offset generator)according to an embodiment of the present invention may change a symboloffset of each OFDM symbol. That is, the random symbol-offset generatormay generate the aforementioned symbol offset. The random symbol-offsetgenerator according to an embodiment of the present invention mayinclude k PN generator. K may be differently set for the respective FFTmodes. According to an embodiment of the present invention, in the caseof 32K FFT mode, 14 bits PN generator may be used. The randomsymbol-offset generator according to an embodiment of the presentinvention may be referred as a sub-PRBS generator which is defined basedon k bits binary word sequence (or binary sequence).

FIG. 67 is a view of a 32K FFT mode random interleaving-sequencegenerator according to an embodiment of the present invention.

The 32K FFT mode random interleaving-sequence generator according to anembodiment of the present invention may include a main-sequencegenerator, a random symbol-offset generator, a modulo operator, amemory-index check and a PRBS control module.

Hereinafter, an operation of each block will be described.

The main-sequence generator may include a toggling and PN generator andmay provide full randomness during interleaving.

The symbol-offset generator may generate a symbol-offset forcyclic-shifting main interleaving-sequence generated by themain-interleaving sequence generator for each OFDM symbol pair. For 32KFFT mode, the symbol-offset generator may include 14 bits PN generator.A detailed operation is the same as those describe above and thus arenot described here.

The modulo operator may be operated when input value exceeds D_(max).D_(max) is used to the interleaving according to an embodiment of thepresent invention and a value of D_(max) may be a half of the value ofthe N_(data)(N_(max)) which is above mentioned. D_(max) for 32K FFT modemay be 16384.

The memory-index check and PRBS control module may not use output fromthe modulo operator when a memory-address is greater than D_(max) andmay repeatedly operate the main-sequence generator to adjust the outputmemory-address such that the output memory-index does not exceedD_(max).

Locations of the illustrated memory-index check and modulo operator canbe changed according to a designer's intention.

FIG. 68 illustrates expressions representing an operation of a 32K FFTmode main-sequence generator and symbol-offset generator according to anembodiment of the present invention.

FIG. 68 (a) shows expressions representing the operation of themain-sequence generator for 32K FFT mode and FIG. 68 (b) showsexpressions representing the operation of the symbol-offset generatorfor 32K FFT mode.

The expressions illustrated in an upper portion of FIG. 68 (a) showinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 14^(th)primitive polynomial and the initial value may be changed by arbitraryvalues. That is, the expressions illustrated in an upper portion showsbinary word sequences or binary bits used to define the main-PRBSgenerator which can generate main-PRBS sequence.

The expressions illustrated in a lower portion of FIG. 68 (a) showprocedures of calculating and outputting the interleaving address forthe interleaving sequence for an output signal of the toggling and thePN generator. As illustrated in the expression, one random symbol-offset(or a symbol offset or cyclic shifting value) is used to calculate theinterleaving sequence and the cyclic shifting value may be applied toeach OFDM symbol pair in the same way.

The parameter q_I may be an order of 0 and 1 which is applied to eachOFDM symbol and be used to an operation of toggling. Consequently, theoperation of toggling for each OFDM symbol can be represented as0,1,0,1, . . . or 1,0,1,0 . . . . In this case, the order of 0 and 1 ofthe parameter q_I can be randomly outputted.

The expressions illustrated in an upper portion of FIG. 68 (b) showsinitial value setting and primitive polynomial of the main-sequencegenerator. In this case, the primitive polynomial may be 14^(th)primitive polynomial and the initial value may be changed by arbitraryvalues.

The expressions illustrated in a lower portion of FIG. 68 (b) shows aprocedure for calculating and outputting a symbol-offset for outputsignals of a toggling and a PN generator. As illustrated in theexpression, the symbol offset (cyclic shifting value) can be calculatedbased on the sub PRBS sequence and the random symbol-offset generatormay be operated for each OFDM symbol pair. Accordingly, the length of anentire output offset may correspond to half of the length of an entireOFDM symbol.

Hereinafter, a random interleaving-sequence generator for 32K FFT modeaccording to another embodiment of the present invention will bedescribed.

The random interleaving-sequence generator for 32K FFT mode according toanother embodiment of the present invention includes a main-sequencegenerator including bit shuffling.

FIG. 69 is a view illustrating a 32K FFT mode randominterleaving-sequence generator according to another embodiment of thepresent invention.

The 32K FFT mode random interleaving-sequence generator according toanother embodiment of the present invention may include a main-sequencegenerator, a symbol-offset generator, a modulo operator, a memory-indexcheck and a PRBS control module.

Details thereof except bit shuffling have been described above and thuswill be omitted here.

The bit shuffling optimizes spreading properties or random propertiesand is designed in consideration of N_(data). In the case of 32K FFTmode, the bit shuffling may use a 14-bit PN generator, which can bechanged.

FIG. 70 is expressions representing operations of 32K FFT mode bitshuffling and 32K FFT mode random interleaving-sequence generatoraccording to another embodiment of the present invention.

(a) illustrates an expression representing an operation of the 32K FFTmode bit shuffling and (b) illustrates an expression representing anoperation of the 32K FFT random interleaving-sequence generator.

The upper portion of (a) shows an operation of the 32K FFT mode bitshuffling and the lower portion of (a) shows an embodiment of the 32KFFT mode bit shuffling for 14 bits.

As illustrated in (a), the 32K FFT mode bit shuffling may mix bits ofregisters of a PN generator during calculation of a memory-index.

An expression illustrated in an upper portion of (b) shows initial valuesetting and primitive polynomial of a main-sequence generator. In thiscase, the primitive polynomial may be 9^(th) primitive polynomial andthe initial value may be changed by arbitrary values. That is, theexpressions illustrated in an upper portion shows binary word sequencesor binary bits used to define the main-PRBS generator which can generatemain-PRBS sequence.

An expression illustrated in a lower portion of (b) shows a procedure ofcalculating and outputting the interleaving address for an interleavingsequence for an output signal of the toggling and the PN generator. Asillustrated in the expression, one random symbol-offset (or a symboloffset or cyclic shifting value) is used to calculate the interleavingsequence and the cyclic shifting value may be applied to each OFDMsymbol pair in the same way.

FIG. 71 is a flowchart illustrating a method for transmitting broadcastsignals according to an embodiment of the present invention.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can encode service data (S71000). Asdescribed above, service data is transmitted through a data pipe whichis a logical channel in the physical layer that carries service data orrelated metadata, which may carry one or multiple service(s) or servicecomponent(s). Data carried on a data pipe can be referred to as the DPdata or the service data. The detailed process of step S71000 is asdescribed in FIG. 1 or FIG. 5-6, FIG. 22.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can time interleave the encodedservice (S71010). The detailed process of this step is as described inFIG. 1, FIG. 5, FIG. 26-29.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention may map the encoded service datainto a plurality of OFDM symbols to build at least one signal frame(S71020). The detailed process of this step is as described in FIG. 7,FIG. 10-21.

Then the apparatus for transmitting broadcast signals according to anembodiment of the present invention may frequency interleave data in thebuilt at least one signal frame (S71030). Then, the apparatus fortransmitting broadcast signals according to an embodiment of the presentinvention may use a different interleaving-seed which is used for everyOFDM symbol pair comprised of two sequential OFDM symbols. as abovedescribed, the basic function of the cell mapper 7010 is to map datacells for each of the DPs, PLS data, if any, into arrays of active OFDMcells corresponding to each of the OFDM symbols within a signal frame.Then, the frequency interleaver 7020 may operate on a single OFDM symbolbasis, provide frequency diversity by randomly interleaving the cellsreceived from the cell mapper 7010. The purpose of the frequencyinterleaver 7020 in the present invention, which operates on a singleOFDM symbol, is to provide frequency diversity by randomly interleavingdata cells received from the cell mapper 7010. In order to get maximuminterleaving gain in a single signal frame (or frame), a differentinterleaving-seed is used for every OFDM symbol pair comprised of twosequential OFDM symbols. The detailed process of the frequencyinterleaving is as described in FIGS. 30 to 70.

Subsequently, the apparatus for transmitting broadcast signals accordingto an embodiment of the present invention may modulate the frequencyinterleaved data by an OFDM scheme (S71040). The detailed process ofthis step is as described in FIG. 1 or 8.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can transmit the broadcast signalsincluding the modulated data (S71050). The detailed process of this stepis as described in FIG. 1 or 8.

FIG. 72 is a flowchart illustrating a method for receiving broadcastsignals according to an embodiment of the present invention.

The flowchart shown in FIG. 72 corresponds to a reverse process of thebroadcast signal transmission method according to an embodiment of thepresent invention, described with reference to FIG. 71.

The apparatus for receiving broadcast signals according to an embodimentof the present invention can receive broadcast signals (S72000). Theapparatus for receiving broadcast signals according to an embodiment ofthe present invention can demodulate the received broadcast signalsusing an OFDM (Orthogonal Frequency Division Multiplexing) scheme(S72010). Details are as described in FIG. 9.

The apparatus for receiving broadcast signals according to an embodimentof the present invention may frequency de-interleave the demodulatedbroadcast signals (S72020). In this case, the apparatus for receivingbroadcast signals according to an embodiment of the present inventioncan perform frequency de-interleaving corresponds to a reverse processof the frequency interleaving as shown in the above. The detailedprocess of the frequency interleaving is as described in FIGS. 30 to 70.

Subsequently, the apparatus for receiving broadcast signals according toan embodiment of the present invention may de-map service data from atleast one signal frame in the frequency de-interleaved broadcast signals(S72030). Details are as described in FIG. 9.

Subsequently, the apparatus for receiving broadcast signals according toan embodiment of the present invention can time de-interleave thede-mapped service data (S72040). Details are as described in FIG. 9.

Subsequently, the apparatus for receiving broadcast signals according toan embodiment of the present invention can decode the timede-interleaved service data (S72050). Details are as described in FIG.9.

As described above, service data is transmitted through a data pipewhich is a logical channel in the physical layer that carries servicedata or related metadata, which may carry one or multiple service(s) orservice component(s). Data carried on a data pipe can be referred to asthe DP data or the service data.

It will be apparent to those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the invention. Thus, it isintended that the present invention covers the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

What is claimed is:
 1. A method for transmitting broadcast signals, themethod comprising: encoding service data by an encoder; mapping theencoded service data onto constellations by a mapper; time interleavingthe mapped service data by a time interleaver; mapping the timeinterleaved service data into at least one signal frame by a framebuilder; frequency interleaving data in the at least one signal frame byusing an interleaving sequence which is generated for an OFDM(Orthogonal Frequency Division Multiplex) symbol pair comprised of twosequential OFDM symbols by a frequency interleaver, wherein theinterleaving sequence is generated based on a main sequence, a symboloffset, and a modulo operation, and wherein an address check operationis applied to the generated interleaving sequence; modulating thefrequency interleaved data by the OFDM scheme by a modulator; andtransmitting the broadcast signals having the modulated data by atransmitter.
 2. The method of claim 1, the method further comprising:bit interleaving the encoded service data.
 3. The method of claim 1,wherein the main sequence is different according to an FFT size.
 4. Themethod of claim 1, wherein the symbol offset is generated for each twosequential OFDM symbols.
 5. An apparatus for transmitting broadcastsignals, the apparatus comprising: an encoder to encode service data; amapper to map the encoded service data onto constellations; a timeinterleaver to time interleave the mapped service data; a frame builderto map the time interleaved service data into at least one signal frame;a frequency interleaver to frequency interleave data in the at least onesignal frame by using an interleaving sequence which is generated for anOFDM (Orthogonal Frequency Division Multiplex) symbol pair comprised oftwo sequential OFDM symbols, wherein the interleaving sequence isgenerated based on a main sequence, a symbol offset, and a modulooperation, and wherein an address check operation is applied to thegenerated interleaving sequence; a modulator to modulate the frequencyinterleaved data by the OFDM scheme; and a transmitter to transmit thebroadcast signals having the modulated data.
 6. The apparatus of claim5, the apparatus further comprising: bit interleaving the encodedservice data.
 7. The apparatus of claim 5, wherein the main sequence isdifferent according to an FFT size.
 8. The apparatus of claim 5, whereinthe symbol offset is generated for each two sequential OFDM symbols.